Digital servo system with loop gain calibration

ABSTRACT

A calibration of a loop gain in a digital servo system is presented. The loop gain can be calibrated measuring the response in a control signal generated by the digital servo system when the control signal is replaced by a sum of the control signal and a sinusoidal disturbance. The loop gain can be set to provide a desired gain, for example unity, between the control signal and the sinusoidal disturbance at a cross-over frequency.

RELATED APPLICATIONS

[0001] This application is related to provisional application Serial No.60/264,351, entitled “Optical Disk Drive Servo System,” by Ron J.Kadlec, Christopher J. Turner, Hans B. Wach, and Charles R. Watt, fromwhich this application claims priority, herein incorporated by referencein its entirety.

CROSS-REFERENCE TO CD-ROM APPENDIX

[0002] CD-ROM Appendix A, which is a part of the present disclosure, isa CD-ROM appendix consisting of twenty two (22) text files. CD-ROMAppendix A is a computer program listing appendix that includes asoftware program executable on a controller as described below. Thetotal number of compact disks including duplicates is two. Appendix B,which is part of the present specification, contains a list of the filescontained on the compact disk. The attached CD-ROM Appendix A isformatted for an IBM-PC operating a Windows operating system.

[0003] A portion of the disclosure of this patent document containsmaterial which is subject to copyright protection. The copyright ownerhas no objection to the facsimile reproduction by anyone of the patentdocument or the patent disclosure, as it appears in the Patent andTrademark Office patent files or records, but otherwise reserves allcopyright rights whatsoever.

[0004] These and other embodiments are further discussed below.

BACKGROUND

[0005] 1. Field of the Invention

[0006] The present invention relates to an optical disk drive and, inparticular, to calibration of a loop gain amplification in a trackingand focus servo system of an optical disk drive.

[0007] 2. Discussion of Related Art

[0008] The need for compact data storage is explosively increasing. Theexplosive increase in demand is fueled by the growth of multimediasystems utilizing text, video, and audio information. Furthermore, thereis a large demand for highly portable, rugged, and robust systems foruse as multimedia entertainment, storage systems for PDA's, cell phones,electronic books, and other systems. One of the more promisingtechnologies for rugged, removable, and portable data storage is WORM(write once read many) optical disk drives.

[0009] One of the important factors affecting design of an opticalsystem (such as that utilized in a WORM drive) is the optical componentsutilized in the system and the control of actuators utilized to controlthe optical system on the disk. The optical system typically includes alaser or other optical source, focusing lenses, reflectors, opticaldetectors, and other components. Although a wide variety of systems havebeen used or proposed, typical previous systems have used opticalcomponents that were sufficiently large and/or massive that functionssuch as focus and/or tracking were performed by moving components of theoptical system. For example, some systems move the objective lens (e.g.for focus) relative to the laser or other light source. It was generallybelieved that the relatively large size of the optical components wasrelated to the spot size, which in turn was substantially dictated bydesigns in which the data layer of a disk was significantly spaced fromthe physical surface of the disk. A typical optical path, then, passedthrough a disk substrate, or some other portion of the disk, typicallypassing through a substantial distance of the disk thickness, such asabout 0.6 mm or more, before reaching a data layer.

[0010] Regardless of the cause being provided for relative movementbetween optical components, such an approach, while perhaps useful foraccommodating relatively large or massive components, presents certaindisadvantages for more compact usage. These disadvantages include arequirement for large form factors, the cost associated withestablishing and maintaining optical alignment between components whichmust be made moveable with respect to one another, and the powerrequired to perform operations on more massive drive components. Suchalignment often involves manual and/or individual alignment oradjustment procedures which can undesirably increase manufacturing orfabrication costs for a reader/writer, as well as contributing to costsof design, maintenance, repair, and the like.

[0011] Many early optical disks and other optical storage systemsprovided relatively large format read/write devices including, forexample, devices for use in connection with 12 inch (or larger) diameterdisks. As optical storage technologies have developed, however, therehas been increasing attention toward providing feasible and practicalsystems which are of relatively smaller size. Generally, a practicalread/write device must accommodate numerous items within its formfactor, including the media, media cartridge (if any), media spin motor,power supply and/or conditioning, signal processing, focus, tracking orother servo electronics, and components associated or affecting thelaser or light beam optics. Accordingly, in order to facilitate arelatively small form-factor, an optical head occupying small volume isdesirable. In particular, it is desirable that the optical head have asmall dimension in the direction perpendicular to the surface of thespinning media. Additionally, a smaller, more compact, optical headprovides numerous specific problems for electronics designed to controlthe position and focus of the optical head.

[0012] Additionally, although larger home systems have little concernregarding power usage, portable personal systems should be low powerdevices. Therefore, it is also important to have a system that conservespower (e.g., by optically overfilling lenses) in both the optical systemand the electronic controlling system.

[0013] Therefore, there is a need for an optical head and optical mediadrive system with a small form factor and, in addition, a servo systemfor controlling the optical head and optical drive system so that datacan be reliably read from and written to the optical media.

SUMMARY

[0014] In accordance with the present invention, a loop gain of a loopgain amplifier in a digital servo system of an optical disk drive ispresented. The optical disk drive system includes a spin motor on whichan optical media is positioned, an optical pick-up unit positionedrelative to the optical media, an actuator arm that controls theposition of the optical pick-up unit, and a control system forcontrolling the spin motor, the actuator arm, and the laser. The controlsystem can include a read/write channel coupled to provide controlsignals to a servo system.

[0015] The optical media can be a relatively small-sized disk withreadable data present on the surface of the disk. Furthermore, theoptical disk may have a pre-mastered portion and a writeable portion.The pre-mastered portion is formed when the disk is manufactured andcontains readable data such as, for example, audio, video, text or anyother data that a content provider may wish to include on the disk. Thewriteable portion is left blank and can be written by the disk drive tocontain user information (e.g., user notes, interactive status (forexample in video games), or other information that the drive or user maywrite to the disk). Because there may be optical differences, forexample in reflectivity, and in the data storage and addressingprotocols between the pre-mastered portion of the disk and the writableportion of the disk, a control system according to the present inventionmay have different operating parameters in the different areas of thedisk.

[0016] The optical pick-up unit can includes a light source, reflectors,lenses, and detectors for directing light onto the optical media. Thedetectors can include laser power feed-back detectors as well as datadetectors for reading data from the optical media. The optical pick-upunit can be mechanically mounted on the actuator arm. The actuator armincludes a tracking actuator for controlling lateral movement across theoptical media and a focus actuator for controlling the position of theoptical pick-up unit above the optical medium. The tracking and focusactuators of the optical pick-up unit are controlled by the controller.

[0017] The servo system includes various servo loops for controlling theoperation of aspects of the optical disk drive, for example the spinmotor, the optical pick-up unit, and the controller. The servo loops,for example, can include combinations of a tracking servo loop and afocus servo loop.

[0018] A method of calibrating a loop gain of a loop gain amplifier in adigital servo system according to the present invention includesreceiving optical signals from an optical pick-up unit in an opticaldisk drive; closing the digital servo system with a first loop gain, thedigital servo system calculating a control signal based on the opticalsignals; applying a sinusoidal disturbance at a cross-over frequency tothe control signal generated by the digital servo system to form asecond control signal; controlling a position of the optical pick-upunit with the second control signal; calculating a discrete Fouriertransform of the sinusoidal disturbance at the cross-over frequency toform a disturbance DFT; calculating a discrete Fourier transform of thecontrol signal to form a signal DFT; calculating a measured loop gainfrom a ratio of the disturbance DFT and the signal DFT; and calculatingthe loop gain from a ratio between the first loop gain and the measuredloop gain.

[0019] In some embodiments the digital servo system is a focus servosystem. In some embodiments, the digital servo system is a trackingservo system. In some embodiments, the measured loop gain, which is thetotal gain of the servo loop, is unity at the cross-over frequency.However, any measured loop gain can be set.

[0020] An optical disk drive according to the present invention includesan optical pick-up unit; an analog processor coupled to receive signalsfrom detectors in the optical pick-up unit and provide digital signals;at least one processor coupled to receive the digital signals, the atleast one processor calculating at least one control signal; and adriver coupled to control a position of the optical pick-up unit inresponse to the at least one control signal. The at least one processorexecutes an algorithm that closes a digital servo system with a loopgain amplifier with a first loop gain, the digital servo systemcalculating a control signal based on the digital signals, applies asinusoidal disturbance at a cross-over frequency to the control signalgenerated by the digital servo system to form a second control signal,substitutes the second control signal for the control signal, calculatesa discrete Fourier transform of the sinusoidal disturbance at thecross-over frequency to form a disturbance DFT, calculates a discreteFourier transform of the control signal to form a signal DFT, calculatesa measured loop gain from a ratio of the disturbance DFT and the signalDFT, and calculates a loop gain from a ratio between the first loop gainand the measured loop gain.

[0021] These and other embodiments of the invention are furtherdescribed below with respect to the following figures.

SHORT DESCRIPTION OF THE FIGURES

[0022]FIG. 1A shows an embodiment of an optical drive according to thepresent invention.

[0023]FIG. 1B shows an example of an optical media that can be utilizedwith an optical drive according to the present invention.

[0024]FIG. 2A shows an embodiment of an optical pickup unit mounted onan actuator arm according to some embodiments of the present invention.

[0025]FIGS. 2B shows an embodiment of an optical pick-up unit accordingto some embodiments of the present invention.

[0026]FIG. 2C illustrates the optical path through the optical pick-upunit of FIG. 2B.

[0027]FIG. 2D shows an embodiment of optical detector positioning of theoptical pick-up unit of FIG. 2B.

[0028]FIGS. 2E and 2F show simplified optical paths as shown in FIG. 2C.

[0029]FIGS. 2G, 2H, 2I, 2J, 2K and 2L illustrate development of a focuserror signal (FES) as a function of distance between the optical pick-upunit and the surface of the optical media in some embodiments of thepresent invention.

[0030]FIGS. 2M, 2N, 2O, 2P, 2Q, and 2R illustrate development of atracking error signal (TES) as a function of position of the opticalpick-up unit over the surface of the optical media in some embodimentsof the present invention.

[0031]FIG. 3A shows a block diagram of a servo system control system ofan optical drive according to some embodiments of the present invention.

[0032]FIG. 3B shows a block diagram of a preamp of FIG. 3A.

[0033]FIG. 4 shows a block diagram of an embodiment of the controllerchip shown in the block diagram of FIG. 3A according to some embodimentsof the present invention.

[0034]FIGS. 5A and 5B show a function block diagram of embodiments of afocus and tracking servo algorithms according to some embodiments of thepresent invention.

[0035]FIG. 5C shows an example transfer function for a low frequencyintegrator as shown in FIGS. 5A and 5B.

[0036]FIG. 5D shows an example transfer function for a phase lead asshown in FIGS. 5A and 5B.

[0037]FIG. 5E and 5F shows an example of a tracking skate detectoraccording to some embodiments of the present invention.

[0038]FIG. 5G shows an embodiment of a direction sensor according tosome embodiments of the present invention.

[0039]FIG. 6 shows an embodiment of a tracking acquisition algorithmexecuted with the algorithms shown in FIGS. 5A and 5B.

[0040]FIGS. 7A, 7B, 7C, and 7D show an embodiment of a focus acquisitionalgorithm executed with the algorithms shown in FIGS. 5A and 5Baccording to some embodiments of the present invention.

[0041]FIGS. 8A and 8B shows an embodiment of a multi-track seekalgorithm according to some embodiments of the present invention.

[0042]FIGS. 9A and 9B show an embodiment of a multi-track seek algorithmexecuted with the algorithms illustrated in the functional block diagramshown in FIGS. 8A and 8B in some embodiments of the present invention.

[0043]FIG. 9C illustrates the temporal hysterisis and amplitudehysterisis of tracking zero cross detection of FIGS. 9A and 9B.

[0044]FIGS. 10A and 10B show demonstrative control signals and a blockdiagram of a one-track jump algorithm of FIGS. 5A and 5B according tosome embodiments of the present invention.

[0045]FIG. 11 shows an embodiment of the DSP firmware architecture forcontrolling and monitoring focus and tracking according to someembodiments of the present invention.

[0046]FIG. 12A shows a block diagram of an embodiment of a calibrationlifetime for a drive according to some embodiments of the presentinvention.

[0047]FIG. 12B shows a chart of parameters and when those parameters arecalibrated through the lifetime of an example drive according to someembodiments of the present invention.

[0048]FIG. 13A shows a block diagram of an embodiment of a calibrationalgorithm according to some embodiments of the present invention whichobtains calibration parameters over various media types and underdifferent conditions.

[0049]FIG. 13B shows a block diagram of an embodiment of a calibrationalgorithm according to some embodiments of the present invention.

[0050]FIG. 14A shows a block diagram of an embodiment of a calibrationalgorithm according to some embodiments of the present invention forcalibrating the detector input offset and gain values.

[0051]FIG. 14B shows a block diagram of an embodiment of a calibrationalgorithm according to some embodiments of the present invention forcalibrating the detector input offsets with light scattering.

[0052]FIGS. 15A and 15B show a block diagram of an embodiment of a FESgain calibration algorithm according to some embodiments of the presentinvention and input signals measured or generated during thecalibration.

[0053]FIG. 16A shows an embodiment of a FES offset calibration algorithmaccording to some embodiments of the present invention.

[0054]FIG. 16B shows another embodiment of an FES offset calibrationalgorithm according to some embodiments of the present invention.

[0055]FIG. 16C shows a graph of the TES peak-to-peak signal as afunction of FES offset illustrating a calibration of the TES offsetaccording to some embodiments of the present invention.

[0056]FIG. 17 shows another embodiment of a FES offset calibrationalgorithm according to some embodiments of the present invention.

[0057]FIG. 18 shows an embodiment of a TES offset calibration algorithmaccording to some embodiments of the present invention.

[0058]FIG. 19 shows another embodiment of a TES offset calibrationalgorithm according to some embodiments of the present invention.

[0059]FIG. 20 shows an embodiment of a TES Gain calibration algorithmaccording to some embodiments of the present invention.

[0060]FIG. 21 shows an embodiment of a loop gain calibration algorithmaccording to some embodiments of the present invention.

[0061]FIG. 22 shows an embodiment of a Bode algorithm according to someembodiments of the present invention.

[0062]FIG. 23 shows an embodiment of a Fourier transform algorithmaccording to some embodiments of the present invention.

[0063]FIG. 24 shows an embodiment of a TES-FES crosstalk calibrationalgorithm according to some embodiments of the present invention.

[0064]FIG. 25 shows an embodiment of a notch filter calibrationalgorithm according to some embodiments of the present invention.

[0065]FIG. 26 shows an embodiment of a feed-forward correction algorithmaccording to some embodiments of the present invention.

[0066]FIGS. 27A and 27B show an embodiment of a zone-calibrationalgorithm according to some embodiments of the present invention.

[0067]FIG. 28 shows an embodiment of an inverse non-linearitycalibration algorithm according to some embodiments of the presentinvention.

[0068]FIG. 29 shows an embodiment of a head load algorithm according tosome embodiments of the present invention.

[0069]FIGS. 30A and 30B show examples of a tracking error signal overthe bar code area.

[0070]FIG. 30C shows an example of a tracking error signal during aclose tracking operation.

[0071] In the figures, elements having the same designation in multiplefigures have the same or similar functions.

DETAILED DESCRIPTION OF THE FIGURES

[0072] The present disclosure was co-filed with the following sets ofdisclosures: the “Tracking and Focus Servo System” disclosures, the“Servo System Calibration” disclosures, the “Spin Motor Servo System”disclosures, and the “System Architecture” disclosures; each of whichwas filed on the same date and assigned to the same assignee as thepresent disclosure, and are incorporated by reference herein in theirentirety. The Tracking and Focus Servo System disclosures include U.S.Disclosure Serial Nos. {Attorney Docket Numbers M-11095 US, M-12077 US,M-12078 US, M-12079 US, M-12080 US, M-12081 US, M-12082 US, M-12083 US,M-12084 US, M-12085 US, M-12086 US, M-12087 US, M-12088 US, M-12089 US,M-12090 US, M-12091 US, M-12092 US, M-12093 US, M-12104 US, M-12105 US,M-12106 US, M-12107 US, M-12108 US, M-12111 US, and M-12112 US.} TheServo System Calibration disclosures include U.S. Disclosure Serial Nos.{Attorney Docket Numbers M-11097 US, M-12094 US, M-12095 US, M-12096 US,M-12097 US, M-12098 US, M-12099 US, M-12100 US, M-12101 US, M-12102 US,M-12103 US, M-12109 US, M-12110 US, and M-12155 US.} The Spin MotorServo System disclosures include U.S. Disclosure Serial Nos. {AttorneyDocket Numbers M-12117 US, M-12118 US, M-12119 US, M-11096 US, M-12121US, M-12122 US, and M-12147 US.} The System Architecture disclosuresinclude U.S. Disclosure Serial Nos. {Attorney Docket Numbers M-11098 US,M-12023 US, M-12024 US, M-12025 US, M-12026 US, M-12027 US, M-12028 US,M-12029 US, M-12030 US, M-12031 US, M-12032 US, M-12120 US, and M-12177US.}

Example of an Optical Disk Drive

[0073]FIG. 1A shows an embodiment of an optical drive 100 according tothe present invention. Optical drive 100 of FIG. 1A includes a spindlemotor 101 on which an optical media 102 is mounted. Drive 100 furtherincludes an optical pick-up unit (OPU) 103 mechanically controlled by anactuator arm 104. OPU 103 includes a light source electricallycontrolled by laser driver 105. OPU 103 further includes opticaldetectors providing signals for controller 106. Controller 106 cancontrol the rotational speed of optical media 102 by controlling spindlemotor 101, controls the position and orientation of OPU 103 throughactuator arm 104, and controls the optical power of the light source inOPU 103 by controlling laser driver 105.

[0074] Controller 106 includes R/W processing 110, servo system 120, andinterface 130. R/W processing 110 controls the reading of data fromoptical media 102 and the writing of data to optical media 102. R/Wprocessing 110 outputs data to a host (not shown) through interface 130.Servo system 120 controls the speed of spindle motor 101, the positionof OPU 103, and the laser power in response to signals from R/Wprocessing 110. Further, servo system 120 insures that the operatingparameters (e.g., focus, tracking, spindle motor speed and laser power)are controlled in order that data can be read from or written to opticalmedia 102.

[0075]FIG. 1B shows an example of optical media 102. Optical media 102can include any combinations of pre-mastered portions 150 and writeableportions 151. Premastered portions 150, for example, can be written atthe time of manufacture to include content provided by a contentprovider. The content, for example, can include audio data, video data,text data, or any other data that can be provided with optical media102. Writeable portion 151 of optical media 102 can be written onto bydrive 100 to provide data for future utilization of optical media 102.The user, for example, may write notes, keep interactive status (e.g.for games or interactive books) or other information on the disk. Drive100, for example, may write calibration data or other operating data tothe disk for future operations of drive 100 with optical media 102. Insome embodiments, optical media 102 includes an inner region 153 closeto spindle access 152. A bar code can be written on a portion of aninner region 153. The readable portion of optical media 102 starts atthe boundary of region 151 in FIG. 1B. In some embodiments, writeableportion 151 may be at the outer diameter rather than the inner diameter.In some embodiments of optical media 102, an unusable outer region 154can also be included.

[0076] An example of optical media 102 is described in U.S. applicationSer. No. 09/560,781 for “Miniature Optical Recording Disk”, hereinincorporated by reference in its entirety. The R/W Data Processing 110can operate with many different disk formats. One example of a diskformat is provided in U.S. application Ser. No. 09/527,982, for“Combination Mastered and Writeable Medium and Use in Electronic BookInternet Appliance,” herein incorporated by reference in its entirety.Other examples of disk data formats are provided in U.S. applicationSer. No. 09/539,841, “File System Management Embedded in a StorageDevice;” U.S. application Ser. No. 09/583,448, “Disk Format forWriteable Mastered Media;” U.S. application Ser. No. 09/542,181,“Structure and Method for Storing Data on Optical Disks;” U.S.application Ser. No. 09/542,510 for “Embedded Data Encryption Means;”U.S. application Ser. No. 09/583,133 for “Read Write File SystemEmulation;” and U.S. application Ser. No. 09/583,452 for “Method ofDecrypting Data Stored on a Storage Device Using an EmbeddedEncryption/Decryption Means,” each of which is herein incorporated byreference in its entirety.

[0077] Drive 100 can be included in any host, for example personalelectronic devices. Examples of hosts that may include drive 100 arefurther described in U.S. patent application Ser. No. 09/315,398 forRemovable Optical Storage Device and System, herein incorporated byreference in its entirety. Further discussions of hosts that may includedrive 100 is provided in U.S. application Ser. No. {Attorney Docket No.M-9115 US} and U.S. application Ser. No. {Attorney Docket No. M-12076US}, each of which is herein incorporated by reference in its entirety.In some embodiments, drive 100 can have a relatively small form factorsuch as about 10.5 mm height, 50 mm width and 40 mm depth.

[0078]FIG. 2A shows an embodiment of actuator arm 104 with OPU 103mounted on one end. Actuator arm 104 in FIG. 2A includes a spindle 200which provides a rotational pivot about axis 203 for actuator arm 104.Actuator 201, which in some embodiments can be a magnetic coilpositioned over a permanent magnet, can be provided with a current toprovide a rotational motion about axis 203 on spindle 200. Actuator arm104 further includes a flex axis 204. A motion of OPU 103 substantiallyperpendicular to the rotational motion about axis 203 can be provided byactivating actuator coil 206. In some embodiments, actuators 206 and 201can be voice coil motors.

[0079]FIGS. 2B and 2C show an embodiment of OPU 103 and an optical raytrace diagram of OPU 103, respectively. OPU 103 of FIG. 2B includes aperiscope 210 having reflecting surfaces 211, 212, and 213. Periscope210 is mounted on a transparent optical block 214. Object lens 223 ispositioned on spacers 221 and mounted onto quarter wave plate (QWP) 222which is mounted on periscope 210. Periscope 210 is, in turn, mountedonto turning mirror 216 and spacer 231, which are mounted on a siliconsubmount 215. A laser 218 is mounted on a laser mount 217 and positionedon silicon submount 215. Detectors 225 and 226 are positioned andmounted on silicon substrate 215. In some embodiments, a high frequencyoscillator (HFO) 219 can be mounted next to laser 218 on siliconsubmount 215 to provide modulation for the laser beam output of laser218.

[0080] Laser 218 produces an optical beam 224 which is reflected intotransparent block 214 by turning mirror 216. Beam 224 is then reflectedby reflection surfaces 212 and 213 into lens 223 and onto optical medium102 (see FIG. 1A). In some embodiments, reflection surfaces 212 and 213can be polarization dependent and can be tuned to reflect substantiallyall of polarized optical beam 224 from laser 218. QWP 222 rotates thepolarization of laser beam 224 so that a light beam reflected fromoptical media 102 is polarized in a direction opposite that of opticalbeam 224.

[0081] The reflected beam 230 from optical medium 102 is collected bylens 223 and focused into periscope 210. A portion (in some embodimentsabout 50%) of reflected beam 230, which is polarized opposite of opticalbeam 224, passes through reflecting surface 213 and is directed ontooptical detector 226. Further, a portion of reflected beam 230 passesthrough reflecting surface 212 and is reflected onto detector 225 byreflecting surface 211. Because of the difference in path distancebetween the positions of detectors 225 and 226, detector 226 ispositioned before the focal point of lens 223 and detector 225 ispositioned after the focal point of lens 223, as is shown in the opticalray diagram of FIG. 2C through 2F.

[0082] In some embodiments, optical surface 212 is nearly 100%reflective for a first polarization of light and nearly 100%transmissive for the opposite polarization. Optical surface 213 can bemade nearly 100% reflective for the first polarization of light andnearly 50% reflective for the opposite polarization of light, so thatlight of the opposite polarization incident on surface 213 isapproximately 50% transmitted. Optical surface 211 can, then, be madenearly 100% reflective for the opposite polarization of light. In thatfashion, nearly 100% of optical beam 224 is incident on optical media102 while 50% of the collected return light is incident on detector 226and about 50% of the collected return light is incident on detector 225.

[0083] A portion of laser beam 224 from laser 218 can be reflected by anannular reflector 252 positioned in periscope 210 on the surface ofoptical block 214. Annular reflector 252 may be a holographic reflectorwritten into the surface of optical block 214 about the position thatoptical beam 224 passes. Annular reflector 252 reflects some of thelaser power back onto a detector 250 mounted onto laser block 217.Detector 250 provides a laser power signal that can be used in a servosystem to control the power of laser 218.

[0084]FIG. 2D shows an embodiment of detectors 225 and 226 which can beutilized with some embodiments of the present invention. Detector 225includes an array of optical detectors 231, 232, and 233 positioned on amount 215. Each individual detector, detectors 231, 232, and 233, iselectrically coupled to provide raw detector signals A_(R), E_(R) andC_(R) to controller 106. Detector 226 also includes an array ofdetectors, detectors 234, 235 and 236, which provide raw detectorsignals B_(R), F_(R), and D_(R), respectively, to controller 106. Insome embodiments, center detectors 232 and 235, providing signals E_(R)and F_(R), respectively, are arranged to approximately optically alignwith the tracks of optical media 102 as actuator arm 104 is rotatedacross optical media 102. In some embodiments, the angle of rotation ofdetectors 225 and 226 with respect to mount 215 is about 9.9 degrees andis chosen to approximately insure that the interference patterns oflight beam 225 reflect back from optical media 102 is approximatelysymmetrically incident with segments 231, 232, 233 of detector 225 andsegments 234, 235 and 236 of detector 226. Non-symmetry can contributeto optical cross-talk between derived servo signals such as the focuserror signal and the tracking error signal.

[0085] A focus condition will result in a small diameter beam 230incident on detectors 225 and 226. The degree of focus, then, can bedetermined by measuring the difference between the sum of signals A_(R)and C_(R) and the center signal E_(R) of detector 225 and the differencebetween the sum of signals B_(R) and D_(R) and the center signal F_(R)of detector 226. Tracking can be monitored by measuring the symmetricplacement of beams 230 on detectors 225 and 226. A tracking monitor canbe provided by monitoring the difference between signals A_(R) and C_(R)of detector 225 and the difference between signals B and D of detector226. Embodiments of OPU 103 are further described in application Ser.No. 09/540,657 for “Low Profile Optical Head,” herein incorporated byreference in its entirety.

[0086]FIG. 2E shows an effective optical ray diagram for light beam 224traveling from laser 218 (FIG. 2B) to optical media 102 (FIG. 1A) indrive 100. Lens 223 focuses light from laser 218 onto optical media 102at a position x on optical media 102. The distance between lens 223 andthe surface of optical media 102 is designated as d. In some embodimentsof the invention, data is written on the front surface of optical media102. In some embodiments, data can be written on both sides of opticalmedia 102. Further, optical media 102 includes tracks that, in mostembodiments, are formed as a spiral on optical media 102 and in someembodiments can be formed as concentric circles on optical media 102.Tracks 260 can differ between premastered and writeable portions ofoptical media 102. For example, tracks 260 in writeable portions 151 ofoptical media 102 include an addressing wobble while tracks inpremastered portion 150 of optical media 102 do not. Data can be writteneither on the land 261 or in the groove 262. For discussion purposesonly, in this disclosure data is considered to be written on land 261 sothat focus and tracking follow land 261. However, one skilled in the artwill recognize that the invention disclosed here is equally applicableto data written in groove 262.

[0087] In premastered portion 150 of optical media 102 (FIG. 1B), datais written as pits or bumps so that the apparent reflective property ofreflected beam 230 changes. Although the actual reflectivity of a bumpis the same as the reflectivity elsewhere on the disk, the apparentreflectivity changes because a dark spot over the premastered marks iscreated due to phase differences in light reflected from the bump versuslight reflected from land 261 around in the bump. The phase differenceis sufficient to cause destructive interference, and thus less light iscollected. Another factor in reducing the amount of light detected fromoptical media 102 at a bump includes the additional scattering of lightfrom the bump, causing less light to be collected.

[0088] In writeable portion 151 of optical media 102 (FIG. 1B), a filmof amorphous silicon provides a mirrored surface. The amorphous siliconcan be written by heating with a higher powered laser beam tocrystallize the silicon and selectively enhances, because the index ofrefraction of the material is changed, the reflectivity and modifies thephase properties of the writeable material in writeable portion 151 ofoptical media 102.

[0089]FIG. 2F shows the reflection of light beam 230 from optical media102 onto detector arrays 225 and 226 of OPU 103. Reflected light beam230 from optical media 102 is collected by lens 223 and focused ondetectors 225 and 226 in OPU 103. Detector 226 is positioned before thefocal point of lens 223 while detector 225 is positioned after the focalpoint of lens 223. As shown in FIG. 2B, the light beam reflected fromoptical media 102 is split at surface 213 to be reflected onto each ofdetectors 225 and 226. Detectors 225 and 226 can then be utilized in adifferential manner to provide signals to a servo control that operatesactuators 201 and 206 to maintain optimum tracking and focus positionsof OPU 103.

[0090]FIG. 2G shows light beam 230 on optical detectors 225 and 226 whend, the distance between lens 223 and the surface of optical media 102,is at an optimum in-focus position. The light intensity of light beam230 reflected from optical media 102 onto detectors 225 and 226 isevenly distributed across segments 231, 232, and 233 of detector 225 andacross segments 234, 235, and 236 of detector 226. FIG. 2H shows thelight beams on detectors 225 and 226 when d is lengthened. The beam ondetector 226 gets larger while the beam on detector 225 gets smaller. Asshown in FIG. 2I, the opposite case is true if distance d is shortened.A focus signal on detector 225, then, can be formed by adding signals Aand C and subtracting signal E. In some embodiments, the resultingsignal is normalized by the sum of signals A, C and E. FIG. 2J shows therelationship of quantity A+C−E as a function of d. FIG. 2K shows therelationship of corresponding quantity B+D−F as a function of d. Thedifference between the two functions shown in FIGS. 2J and 2K is shownin FIG. 2L. In FIG. 2L, the focus point can be at the zero-crossing ofthe curve formed by taking the difference between the graphs of FIGS. 2Jand 2K as a function of focus distance d. In the preceding discussion,subscripts are dropped from the detector signals A, C, E, B, D, and F toindicate that the discussion is valid for the analog or digital versionsof these signals.

[0091]FIG. 2M shows beam of light 230 on each of detectors 225 and 226in an on-track situation. As shown in FIG. 2E, light from laser 218 isincident on optical media 102 which has tracks 260 with lands 261 andgrooves 262. The beam is broad enough that interference patterns areformed in the reflected light beam that, as shown in FIG. 2F, isincident on detectors 226 and 225. As shown in FIG. 2M, the interferencepattern forms an intensity pattern with most of the intensity centeredon elements 232 and 235, the center elements of detectors 225 and 226,respectively, where constructive interference from tracks 260 is formed.Lower intensity light, where destructive interference is formed, isincident on outside elements 231 and 233 of detectors 225, 234 and 236of detector 226. If light beam 224 from laser 218 is focused on edges oftracks 260, the interference pattern shifts. FIGS. 2N and 2O showinterference patterns indicative of light at edges of tracks 260. Since,when the light beam is “on-track” the intensity of light in outsideelements 231 and 233 and outside elements 234 and 236 are the same, atracking signal can be formed by the difference in signals A and C and Band D. FIG. 2P shows the normalized value A−C as a function of x aslight beam 224 from laser 218 is moved over the surface of optical media102. FIG. 2Q shows the normalized value of B−D as a function of x. Ineach case, a sinusoidal function is generated where an on-trackcondition is met at zero-crossings. Because detectors 225 and 226 aredifferential in nature, and because the relationship shown in FIG. 2Q isout of phase with that shown in FIG. 2P, an overall tracking errorsignal can be formed by taking the difference between the calculationsshown in FIG. 2P and the calculations shown in FIG. 2Q as an indicationof tracking error. Variation over a complete period of the sine waveshown in FIG. 2Q indicates a full track crossing. In other words, azero-crossing will indicate either land 261 or groove 262 of track 260.The slope of the tracking error signal (TES) at the zero crossing canindicate whether the crossing is through a groove or through a land intrack 260.

[0092] Utilizing detectors 225 and 226 in a normalized and differentialmanner to form tracking and focus error signals minimizes thesensitivity of drive 100 to variations in laser power or to slightdifferences in reflectivity as optical media 102 is rotated. Variationscommon to both detectors 225 and 226 are canceled in a differentialmeasurement. Further, although best tracking and best focus may occur atzero points in the TES or FES signals, these locations may not beoptimum for the best reading or writing of data. Since the purpose ofdrive 100 is to read and write data to optical media 102, in someembodiments different operating points may be made thus allowing drive100 to switch between optimum servo function and optimum data readfunction. This factor is further discussed below with respect to the TESand FES servo algorithms.

[0093] Further, there can be significant cross-talk between the TES andFES signals as described above with FIGS. 2A through 2R. FES, as definedabove for each of detectors 225 and 226, will depend on TES as OPU 103passes over tracks on optical media 102. With the observation that thecross-talk intensity changes are concentrated on the outer elements(e.g., elements 231 and 233 of detector 225) and that the sum signal isnot dependent on spot size, so long as the spot stays on detector 225,then FES can be defined such that cross-talk is reduced or eliminated.For example, with detector 225 FES is defined as (A+C−E)/(A+C+E). Sincethe cross-talk in the outer elements (elements 231 and 233) have a largecrosstalk the cross-talk in the central element, element 232, is smallerand out of phase with the cross-talk in the outer elements, thencross-talk can be reduced by defining a new FES, NFES, as FES−SUM, whereSUM is A+C+E. In some embodiments, NFES can be FES−HP(SUM), whereHP(SUM) is a high-pass filtered sum signal with a filter gain chosen toreduce cross-talk. In some embodiments, NFES can be normalized with theSUM signal or with a low-pass filtered SUM signal. In differential mode,i.e. with both detectors 225 and 226, the new FES signal with reducedcross-talk can be defined, as above, by the difference between the FESsignal calculated from detector 225 and the FES signal calculated fromdetector 226.

[0094] Embodiments of drive 100 (FIG. 1A) present a multitude ofchallenges in control over conventional optical disk drive systems. Aconventional optical disk drive system, for example, performs atwo-stage tracking operation by moving the optics and focusing lensradially across the disk on a track and performs a two-stage focusingoperation by moving a focusing lens relative to the disk. Actuators 201and 206 of actuator arm 104 provide a single stage of operation that,nonetheless in some embodiments, performs with the same performance asconventional drives with conventional optical media. Further,conventional optical disk drive systems are much larger than someembodiments of drive 100. Some major differences include the actuatorpositioning of actuator arm 104, which operates in a rotary fashionaround spindle 200 for tracking and with a flexure action around axis204 for focus. Further, the speed of rotation of spindle driver 101 isdependent on the track position of actuator arm 104. Additionally, thecharacteristics of signals A_(R), B_(R), C_(R), D_(R), E_(R), and F_(R)received from OPU 103 differ with respect to whether OPU 103 ispositioned over a premastered portion of optical media 102 or awriteable portion of optical media 102. Finally, signals A_(R), B_(R),C_(R), D_(R), E_(R), and F_(R) may differ between a read operation and awrite operation.

[0095] It may generally be expected that moving to a light-weightstructural design from the heavier and bulkier conventional designs,such as is illustrated with actuator arm 104, for example, may reducemany problems involving structural resonances. Typically, mechanicalresonances scale with size so that the resonant frequency increases whenthe size is decreased. Further, focus actuation and tracking actuationin actuator arm 104 are more strongly cross-coupled in actuator arm 104,whereas in conventional designs the focus actuation and trackingactuation is more orthogonal and therefore more decoupled. Further,since all of the optics in drive 100 are concentrated at OPU 103, alarger amount of optical cross-coupling between tracking and focusmeasurements can be experienced. Therefore, servo system 120 has to pushthe bandwidth of the servo system as hard as possible so that nomechanical resonances in actuator arm 104 are excited while notresponding erroneously to mechanical and optical cross couplings.Furthermore, due to the lowered bandwidth available in drive 100,nonlinearities in system response can be more severe. Further, sincedrive 100 and optical media 102 are smaller and less structurally exact,variations in operation between drives and between various differentoptical media can complicate control operations on drive 100.

[0096] One of the major challenges faced by servo system 120 of controlsystem 106, then, includes operating at lower bandwidth with largeamounts of cross coupling and nonlinear system responses, andsignificant variation in servo characteristics between different opticalmedia and between different optical drives. Additionally, theperformance of drive 100 should match or exceed that of conventional CDor DVD drives in terms of track densities and data densities.Additionally, drive 100 needs to maintain compatibility with othersimilar drives so that optical media 102 can be removed from drive 100and read or written to by another similar drive.

[0097] Conventional optical drive servo systems are analog servos. In ananalog environment, the servo system is limited with the constraints ofanalog calculations. Control system 106, however, can includesubstantially a digital servo system. A digital servo system, such asservo system 120, has a higher capability in executing solutions toproblems of system control. A full servo loop is formed when servosystem 120 is coupled with actuator 104, OPU 103, spin motor 101 andoptical media 102, where the effects of a control signal generated byservo system 120 is detected. A full digital servo system is limitedonly by the designer's ability to write code, the memory storageavailable in which to store data and code, and processor capabilities.Embodiments of servo system 120, then, can operate in the harshercontrol environment presented by disk drive 100 and are capable ofhigher versatility towards upgrading servo system 120 and for refinementof servo system 120 than in conventional systems.

[0098] Drive 100 can also include error recovery procedures. Embodimentsof drive 100 which have a small form factor can be utilized in portablepackages and are therefore subject to severe mechanical shocks andtemperature changes, all of which affect the ability to extract data(e.g., music data) from optical media 102 reliably or, in some cases,write reliably to optical media 102. Overall error recovery and controlsystem 106 is further discussed in the System Architecture disclosures,while tracking, focus and seek algorithms are discussed below, and inthe Tracking and Focus Servo System disclosures. Further, since drive100, therefore, has tighter tolerances than conventional drives, someembodiments of servo-system 120 include dynamic calibration procedures,which is further described in the Servo System Calibration disclosures.Control of the spin motor 101 is described in the Spin Motor ServoSystem disclosures. The System Architecture disclosures, the Trackingand Focus Servo System disclosures, the Servo System Calibrationdisclosures, and the Spin Motor Servo System disclosures have beenincorporated by reference into this disclosure.

Example Embodiment of an Optical Drive Controller

[0099]FIG. 3A shows a block diagram of an embodiment of controller 106according to the present invention. Optical signals are received fromOPU 103 (see FIGS. 2B-2D). As discussed above with FIGS. 2B, 2C and 2D,some embodiments of OPU 103 include two detectors with detector 225including detectors 231, 232, and 233 for providing detector signalsA_(R), E_(R), and C_(R), respectively, and detector 226 having detectors234, 235 and 236 providing detector signals B_(R), F_(R), and D_(R),respectively. Further, some embodiments of OPU 103 include a laser powerdetector 250 mounted to receive reflected light from an annularreflector 252 positioned on periscope 210, as discussed above, andtherefore provides a laser power signal LP_(R) as well.

[0100] Detector signals received from OPU 103 are typically currentsignals. Therefore, the detector signals from OPU 103 are converted tovoltage signals in a preamp 310. Preamp 310 includes a transimpedanceamplifier, which converts current signals to voltage signals. Further,preamp 310 generates a high frequency (HF) signal based on the detectorsignals from OPU 103. The HF signal can be utilized as the data signaland is formed by the analog sum of the signals from OPU 103 (signalsA_(v), B_(v), C_(v), D_(v), E_(v) and F_(v) in FIG. 3A).

[0101]FIG. 3B shows a block diagram of an embodiment of preamp 310.Preamp 310 includes an array of transimpedance amplifiers, amplifiers311, 312, 313, 314, 315, 316 and 317 in FIG. 3B. Amplifier 311 receivesthe laser power signal LP_(R) from OPU 103 and amplifiers 312 through317 receive signals A_(R) through F_(R), respectively, from OPU 103. Ingeneral, preamp 310 can receive any number of detector signals from OPU103. In some embodiments, each of signals A_(R) through F_(R) and laserpower LP_(R) are current signals from detectors 225, 226 and 250 of OPU103. Amplifiers 311 through 317 output voltage signals LP_(v), A_(v),B_(v), C_(v), D_(v), E_(v), and F_(v), respectively. The gain of each ofamplifiers 311 through 317, G1 through G7, can be set by gain conversion318. Gain conversion 318 can receive a W/R gain switch that indicates aread or a write condition and can adjust the gains G1 through G7 ofamplifiers 311 through 317 accordingly. In some embodiments, gainconversion 318 receives gain selects for each of gains G1 through G7 anda forward sensor FWD sensor. In some embodiments, gains G1 and G2 arethe same and gains G3 through G6 are the same. In some embodiments,gains G3 through G6 are approximately ½ of gains G1 and G2.

[0102] Since the laser power required for a write operation is muchhigher than the laser power required for a read operation, the gains G1through G7 can be set high for a read operation and can be lowered for awrite operation. In some embodiments, gain conversion 318 outputs one ofa number (e.g., two) of preset gains for each of gains G1 through G7 inresponse to the W/R gain switch setting. Summer 319 receives each of thesignals A_(v), B_(v), C_(v), D_(v), E_(v), and F_(v) from amplifiers 312through 317, respectively, and outputs a differential HF signal. In someembodiments, the differential HF signal is the analog sum of signalsA_(v), B_(v), C_(v), D_(v), E_(v), and F_(v). The differential HF signalindicates the total light returned from optical medium 102 (see FIG. 1)and therefore includes, in a read operation, the actual data read fromoptical medium 102.

[0103] In some embodiments, preamplifier 308 can include summers 331through 336, which receives the output signals from amplifiers 312through 317, respectively, and offsets the output values from amplifiers312 through 317, respectively, by reference voltages VREF6, VREF5, VRD4,VRD3, VRD2, and VRD1, respectively. In some embodiments VRD1 throughVRD4 are the same and VREF5 and VREF6 are the same. The input signals todifferential summer 319, then, are the output signals from adders 331through 336 and the output signal from amplifier 311.

[0104] As shown in FIG. 3A, the voltage signals LP_(v), A_(v), B_(v),C_(v), D_(v), E_(v), F_(v), and HF from preamp 310 are input signals tocontrol chip 350. Control chip 350 can be a digital and analog signalprocessor chip which digitally performs operations on the input signalsA_(v), B_(v), C_(v), D_(v), E_(v), F_(v), HF, and LPV to control theactuators of actuator arm 104 (FIG. 1), the laser power of laser 218(FIG. 2B), and the motor speed of spindle motor 101 (FIG. 1). Control350 also operates on the HF signal to obtain read data and communicatedata and instructions with a host (not shown). In some embodiments,control 350 can be a ST Microelectronics 34-00003-03.

[0105] The laser power signal LP_(v) is further input to laser servo 105along with a W/R command, indicating a read or a write operation. Insome embodiments, laser servo 105 is an analog servo loop that controlsthe power output of laser 218 of OPU 103. In some embodiments, the laserpower can also be included in a digital servo loop controlled by controlchip 350. The laser power of laser 218 is high for a write operation andlow for a read operation. Laser servo 105, then, holds the power oflaser 218 to a high power of low power in response to the laser W/Rpower control signal from control chip 350. Analog servo systems forutilization as laser servo 105 are well known to one skilled in the art.In some embodiments, laser servo 105 can also be a digital servo system.

[0106] Control chip 350 is further coupled with data buffer memory 320for buffering data to or from the host and program memory 330. Programmemory 330 holds program code for, among other functions, performing theservo functions for controlling focus and tracking functions, laserpower, and motor speed. Data read through OPU 103 can be buffered intodata buffer memory 320, which assists in power savings and allows moretime for error recovery if drive 100 suffers a mechanical shock or otherdisturbing event. In some embodiments, control chip 350 activatesmechanical components 107 of drive 100 when data buffer 320 is depletedand deactivates mechanical portions 107 when buffer 320 is filled. Servosystem 120, then, needs only to be active while mechanical portions 107are active.

[0107] In some embodiments, control chip 350 is a low power device thatoperates at small currents. Therefore, control voltages for controllingfocus and tracking actuators (through coils 206 and 201, respectively)are input to power driver 340. Power driver 340 outputs the currentrequired to affect the focus and tracking functions of actuator arm 104through focus actuator 206 and tracking actuator 201. In someembodiments, as described above, focus actuator 206 and trackingactuator 201 are voice coil motors mounted on actuator arm 104 so thattracking actuator 201 moves OPU 103 over tracks of optical media 102 andfocus actuator 206 flexes actuator arm 104 to affect the distancebetween OPU 103 and optical media 102.

[0108] Driver 340 can also provide current to drive spindle motor 101.Spindle motor 101 provides sensor data to a servo system and can also beresponsive to the tracking position of OPU 103 so that the speed ofspindle motor 101 is related to the track. In some embodiments, the datarate is held constant by controlling the speed of spindle motor 101 asOPU 103 tracks across optical media 102. A servo system for controllingspindle motor 101 is further described in the Spin Motor Servo Systemdisclosures.

[0109] Further, power drivers 340 can also control a cartridge ejectmotor 360 and latch solenoid 370 in response to commands from controlchip 350. Cartridge eject motor 360 mounts and dismounts optical media102 onto spindle motor 101. Latch solenoid 370 provides a secured latchso that the OPU 103 does not contact optical media 102 duringnon-operational shock conditions.

[0110] Finally, system 300 can include power monitor 380 and voltageregulators 390. Power monitor 380 provides information about the powersource to control chip 350. Control chip 350, for example, can be resetby power monitor 380 if there is a power interruption. Voltageregulators 390, in response to an on/off indication from control chip350, provides power to drive laser 218, as well as control chip 350 andpre-amp 310. Spindle motor 101, actuators 206 and 201, cartridge ejectmotor 360, and latch solenoid 370 can be powered directly from the inputvoltage.

[0111]FIG. 4 shows an embodiment of control chip 350 of control system300. The embodiment of control chip 350 shown in FIG. 4 includes amicroprocessor 432 and a digital signal processor (DSP) 416. Since DSP416 operates much faster, but has lower overall capabilities (e.g., codeand data storage space), than microprocessor 432, in some embodimentsreal time digital servo system algorithms can be executed on DSP 416while other control functions and calibration algorithms can be executedon microprocessor 432. A control structure for embodiments of controlchip 350, and interactions between DSP 416 and microprocessor 432, arefurther discussed in the System Architecture disclosures.

[0112] Control chip 350 receives voltage signals A_(v), E_(v), C_(v),B_(v), F_(v), D_(v), HF, and LP_(v) from preamp 310 (see FIG. 3A).Signals A_(v), E_(v), C_(v), B_(v), F_(v), and D_(v) are input intooffset blocks 402-1 through 402-6, respectively. Offset blocks 402-1through 402-6 provide a variable offset for each of input signals A_(v),E_(v), C_(v), B_(v), F_(v), and D_(v). The value of the offset isvariable and can be set by a calibration routine executed inmicroprocessor 432 or DSP 416, which is further described below.

[0113] In some embodiments, the offset values can be set so that whenthe power of laser 218 is off the output signal from each of offsets402-1 through 402-6 is zero, i.e. a dark-current calibration. In someembodiments, the effects of light scattering in OPU 103 may also bededucted in offset 402-1 through 402-6.

[0114] The signals output from offsets 402-1 through 402-6 are input tovariable gain amplifiers 404-1 through 404-6, respectively. Again, thegains of each of variable gain amplifiers 404-1 through 404-6 are set bya calibration routine executed in microprocessor 432 or DSP 416, asfurther described below. In some embodiments, the gains of amplifiers404-1 through 404-6 can be set so that the dynamic range ofanalog-to-digital converters 410-1 and 410-2 are substantially fullyutilized in order to reduce quantization error.

[0115] The offsets and gains of offsets 402-1 through 402-6 and 404-1through 404-6, respectively, may be different for each of signals A_(v),E_(v), C_(v), B_(v), F_(v), and D_(v). Further, the gains and offsetsmay be different for read operations and write operations and may bedifferent for pre-mastered verses writeable portions of optical media102. Further, the offsets and gains may vary as a function of trackingposition on optical media 102 (in addition to simply varying betweenpremastered or writeable regions). Some factors which may further leadto different offset and gain settings include light scattering ontodetectors, detector variations, detector drift, or any other factorwhich would cause the output signal from the detectors of OPU 103 tovary from ideal output signals. Various calibration and feedbackroutines can be operated in microprocessor 432 and DSP 416 to maintainefficient values of each of the offset and gain values of offsets 402-1through 402-6 and amplifiers 404-1 through 404-6, respectively, overvarious regions of optical media 102, as is further discussed below.

[0116] Therefore, in some embodiments the offset and gain values ofoffsets 402-1 through 402-6 and amplifiers 404-1 through 404-6 can bevaried by microprocessor 432 and DSP 416 as OPU 103 is positionallymoved over optical media 102. Additionally, in some embodimentsmicroprocessor 432 and DSP 416 monitor the offset and gain values ofoffset 402-1 through 402-6 and amplifiers 404-1 through 404-6 in orderto dynamically maintain optimum values for the offset and gain values asa function of OPU 103 position over optical media 102. In someembodiments, offset and gain values are set in a calibration algorithm.In some embodiments, the offset values of offsets 402-1 through 402-6are determined such that the dynamic range of the respective inputsignals are centered at zero. Further, the gains of amplifiers 404-1through 404-6 are set to fill the dynamic range of analog-to-digitalconverters 410-1 and 410-2 in order to reduce quantization error. Insome embodiments, the gains of amplifiers 404-1 through 404-6 can bemodified in error recovery routines. See the System Architecturedisclosures. In some embodiments, the gains of amplifiers 404-1 through404-6 can be optimized through continuous performance monitoring. Seethe Servo System Calibration disclosures.

[0117] The output signals from variable gain amplifiers 404-1 through404-6 are input to anti-aliasing filters 406-1 through 406-6,respectively. Anti-aliasing filters 406-1 through 406-6 are low-passfilters designed to prevent aliasing. In some embodiments, the outputsignals from each of anti-aliasing filters 406-1 through 406-5 are inputto analog-to-digital converters. In other embodiments, a limited numberof analog-to-digital converters are utilized. In the embodiment shown inFIG. 4, the output signals from anti-aliasing filters 406-1 through406-5 are input to multiplexers 408-1 and 408-2. The output signals fromanti-aliasing filters 406-1 through 406-3 are input to multiplexer 408-1and the output signals from anti-aliasing filters 406-4 through 406-6are input to multiplexer 408-2.

[0118] The HF signal from preamp 310 (see FIG. 3A) can be input toequalizer 418. Equalizer 418 equalizes the HF signal by performing atransform function that corrects systematic errors in detecting andprocessing data read from optical media 102. In some embodiments,equalizer 418 operates as a band-pass filter. The output signal fromequalizer 418 is input to amplifier 420. The output signal fromamplifier 420 can be input as a fourth input to multiplexer 408-1.

[0119] The laser power signal LP_(v) can be input to multiplexer 436where LP_(v) can be multiplexed with other signals that may requiredigitization. The output signal from multiplexer 436 can then be inputas a fourth input to multiplexer 408-2. One skilled in the art willrecognize that if no other signals are being digitally monitored,multiplexer 436 can be omitted. Further, one skilled in the art willrecognize that any number of analog-to-digital converters can beutilized and any number of signals can be multiplexed to utilize theavailable number of analog-to-digital converters. The particularembodiment shown here is exemplary only.

[0120] The output signal from multiplexer 408-1 is input toanalog-to-digital converter 410-1. The output signal from multiplexer408-2 is input to analog-to-digital converter 410-2. Analog-to-digitalconverters 410-1 and 410-2 can each include registers 478 for thestorage of digitized values. ADC 410-1 includes registers 478-1 through478-4 and ADC 410-2 includes registers 478-5 through 478-8. Further,multiplexers 408-1 and 408-2 and ADC 410-1 are coupled to a clock 476which determines which signals from multiplexers 408-1 and 408-2 arecurrently being digitized and, therefore, in which of register 478-1through 478-4 the result of that digitization should be stored. In someembodiments, analog-to-digital converters 410-1 and 410-2 can be, forexample, 10 bit converters sampling at a rate of about 26 Mhz, with eachsample being taken from a different input of multiplexers 408-1 and408-2, respectively. In some embodiments ADC 410-1 and 410-2 can samplethe output signals from anti-aliasing filters 406-1 through 406-6 at ahigher rate than other signals, for example the LP_(v), signal or theoutput signal from gain 420. In some embodiments, for example, ADC 410-1and 410-2 may sample each of the output signals from anti-aliasingfilters 406-1 through 406-6 at an effective sampling rate of about 6.6MHz.

[0121] The digitized signals from analog-to-digital converts 410-1 and410-2, then, are the digitized and equalized HF signal HF_(d), thedigitized laser power signal LP_(d), and digitized detector signalsA_(d), E_(d), C_(d), B_(d), F_(d), and D_(d). Digitized laser powersignal LP_(d) is input to DSP 416 and can be utilized in a digital servoloop for controlling laser power or in determination of gain and offsetvalues for various components. Alternatively, DSP 416 or microprocessor432 can monitor LP_(d) to determine error conditions.

[0122] The digitized HF signal HF_(d) can be input to focus OK (FOK)412, which outputs a signal to DSP 416 and microprocessor 432 indicatingwhether focus is within a useful range. Detectors 225 and 226 are sizedsuch that, when OPU 103 is seriously out of focus, light is lost offdetectors 225 and 226. Therefore, FOK 412 determines if the totalintensity of light on detectors 225 and 226 is above a FOK thresholdvalue indicating a near in-focus condition. In some embodiments, thisfunction can also be executed in software rather than hardware. Further,the FOK threshold value can be fixed or can be the result of acalibration algorithm. In some embodiments, the FOK threshold value canbe dependent upon the type of media on optical media 102 that OPU 103 iscurrently over.

[0123] Digitized detector signals A_(d), E_(d), C_(d), B_(d), F_(d), andD_(d) are input to decimation filters 414-1 through 414-6, respectively.Decimation filters 414-1 through 414-6 are variable filters whichdown-sample the digitized detector signals A_(d), E_(d), C_(d), B_(d),F_(d), and D_(d) to output signals A_(f), E_(f), C_(f), B_(f), F_(f),and D_(f), which are input to DSP 416. In some embodiments, for example,each of signals A_(d), E_(d), C_(d), B_(d), F_(d), and D_(d) haseffectively been sampled at 6.6 MHz by ADC 410-1 and 410-2. Decimationfilters 414-1 through 414-6 can then down-sample to output signalsA_(f), E_(f), C_(f), B_(f), F_(f), and D_(f) at, for example, about 70kHz. Embodiments of decimation filters 414-1 through 414-6 candown-sample to any sampling rate, for example from about 26 kHz to about6.6 MHz.

[0124] The effects of down-sampling in decimation filters 414-1 through414-6 include an averaging over several samples of each of signalsA_(d), E_(d), C_(d), B_(d), F_(d), and D_(d). This averaging provides alow-pass filtering function and provides higher accuracy for signalsA_(f), E_(f), C_(f), B_(f), F_(f), and D_(f) which are actually read byDSP 416 and utilized in further calculations. In some embodiments, theaccuracy is effectively increased to 13 bits from the 10 bit outputsignals from ADC 410-1 and 410-2.

[0125] Further, although the data signals included in the HF signal canbe at high frequency (e.g., several MHz), the servo information is atmuch lower frequencies. In some embodiments, the mechanical actuators206 and 201 of actuator arm 104 can respond to changes in the hundredsof hertz range yielding servo data in the 10s of kilohertz range, ratherthan in the Megahertz ranges of optical data. Further, mechanicalresonances of actuator arm 104 can occur in the 10's of kilohertz range.Therefore, down-sampling effectively filters out the high frequencyportion of the spectrum that is not of interest to servo feedbacksystems. Further, a much cleaner and more accurate set of digital servosignals A_(f), E_(f), C_(f), B_(f), F_(f), and D_(f) are obtained by theaveraging performed in decimation filters 414-1 through 414-6,respectively. In some embodiments, decimation filters 414-1 through414-6 can be programmed by microprocessor 432 or DSP 416 to set theoutput frequency, filtering characteristics, and sampling rates.

[0126] In particular, a tracking wobble signal at about 125 KHz in thetrack on writeable portions 151 of optical media 102 results from aslight modulation in the physical track in that region. This wobble isfiltered out of signals A_(f), E_(f), C_(f), B_(f), F_(f), and D_(f) byfiltering provided in decimation filters 414-1 through 414-6. Actuatorarm 104 cannot respond to control efforts in this frequency range.Similarly, a stabilizing frequency on laser power at 500 MHz, frommodulator 219 (see FIG. 2B), is filtered out of signals A_(f), E_(f),C_(f), B_(f), F_(f), and D_(f) by filtering provided in decimationfilters 414-1 through 414-6. For servo purposes, only the lowerfrequency region of the signals are important. Then, the signals A_(f),E_(f), C_(f), B_(f), F_(f), and D_(f) only include sensor noise and realdisturbances that can be followed by a servo system operating on, forexample, actuator arm 104. Those disturbances can include physicalvariations due to stamping errors in the mastering process, since trackswill not be perfectly laid. In addition, spindle motor 101 may providesome errors through bearings that cause vibration. Additionally, opticalmedia 102 may not be flat. Tracking and focus servo functions, as wellas the servo systems tracking laser power and the rotational speed ofspindle motor 101, can follow these errors. Further, it is importantthat the spectral response of a servo system be responsive to thefrequency range of the errors that are being tracked. If not, then theservo system may make the tracking and focus environments worse.Further, embodiments of drive 100 operate in extremes of physical abuseand environmental conditions that may alter the resonant frequencycharacteristics and response characteristics of spindle motor 101,optical media 102, and actuator arm 104 during operation in the shortterm or during the lifetime of drive 100 or optical media 102. A servosystem according to the present invention should be insensitive to thesechanging conditions.

[0127] The digital output signals A_(d), E_(d), C_(d), B_(d), F_(d), andD_(d) are further input to summer 438. Summer 438 can be a programmablesummer so that a sum of particular combinations of inputs A_(d), E_(d),C_(d), B_(d), F_(d), and D_(d) can be utilized. Summer 438 sums aselected set of signals A_(d), E_(d), C_(d), B_(d), F_(d), and D_(d) toform a low-bandwidth digitized version of the HF signal. The outputsignal from summer 438 is multiplexed in multiplexer 441 and multiplexer443 with the digitized HF signal HF_(d) output from ADC 410-1. A HFselect signal input to each of multiplexer 441 and 443 selects which ofHF_(d) or the output signal from summer 438 are chosen as the outputsignal from multiplexer 441 and 443. The output signal from multiplexer441 is input to disturbance detector 440. Disturbance detector 440detects defects on media 102 by monitoring the data signal representedby HF_(d) or the output from summer 438 and alerts DSP 416 of a defect.A defect can include a scratch or speck of dust on optical media 102.Results of defects manifest themselves as sharp spikes in the inputsignal. In some embodiments, disturbance detector 440 can include a lowpass filter. The input signal to disturbance detector 440 is low passfiltered and the filtered signal is compared with the unfiltered inputsignal. If the difference exceeds a pre-set defect threshold signal,then a defect flag is set. The defect flag can be input to DSP 416 ormicroprocessor 432.

[0128] The output signal from multiplexer 443 is also input to mirrordetector 442. Mirror detector 442 provides a signal similar to the TES,but 90 degrees out of phase. DSP 416 receives the mirror signal and, incombination with the TES calculated within DSP 416, can determinedirection of motion while track seeking. The TES is a sine wave thatindicates a track jump over one period of the wave. If a tracking servosystem attempts to track at the zero-crossing with an improper slope,the servo system will simply move actuator arm 104 away from thatzero-crossing. The mirror signal can be utilized to indicate if themotion is in the proper direction.

[0129] Additionally, signals A_(d) and C_(d) are received in summer 444,which calculates the value A_(d)-C_(d). Further, signals B_(d) and D_(d)are input to summer 446 which calculates the value B_(d)-D_(d). Theoutput signals from summer 444 and summer 446 are input to summer 448,which takes the difference between them forming a version of trackingerror signal, TES, from the digitized detector output signals. Theoutput signal from summer 448 is input to a bandpass filter 450. Theoutput signal from bandpass filter 450 is PushPullBP. The output signalfrom summer 448 is further input to a lowpass filter 452. The outputsignal from lowpass filter 452 is input to track crossing detector 454which determines when the TES calculated by summer 448 indicates thatOPU 103 has crossed a track on optical media 102. The output signal fromtrack crossing detector 454 is the TZC signal and is input to DSP 416.

[0130] The low-pass filtered TES is a sine wave as a function ofposition of OPU 103 over optical media 102. (See, e.g., FIG. 2R). Aone-period change in TES indicates a track crossing. Then, in someembodiments track crossing detector 454 can output a TZC pulse wheneverthe TES crosses zero (which results in two pulses per track crossing).In some embodiments, track crossing detector 454 can generate a pulsewhenever a zero crossing having the proper slope in the TES curve isdetected.

[0131] The signal PushPullBP can be input to Wobble/PreMark detector428. In some embodiments, in the writeable portion of optical media 102the tracks have a predetermined wobble, resulting from an intentionalmodulation in track position, which has a distinct frequency. In someembodiments, the wobble frequency of PushPullBP is in the 100 kHz range(in some embodiments around 125 kHz) and therefore, with decimationfilters 414-1 through 414-6 operating as a low-pass filter at around 70kHz, is filtered out of signals A_(f), E_(f), C_(f), B_(f), F_(f), andD_(f). Bandpass filter 450 can be set to pass TES signals of thatfrequency so that detector 428 detects the wobble in the track.

[0132] The frequency of wobble in the track from detector 428 isindicative of the rotational speed of spindle driver 101. Further, aspindle speed indication from spindle motor 101 itself can be directlyinput to microprocessor 432 and DSP 416. Further, the signal from gain420 can be input to slicer 422, DPLL 424, and Sync Mark Detector 426 toprovide a third indication of the speed of spindle motor 101. Slicer 422determines a digital output in response to the output signal fromequalizer 418 and amplifier 420. Slicer 422 simply indicates a highstate for an input signal above a threshold value and a low state for aninput signal below the threshold. DPLL 424 is a digital phase-lockedloop, which basically servos a clock to the read back signal so thatsync marks on the tracks can be detected. Sync mark detector 426, then,outputs a signal related to the period between detected sync marks,which indicates the rotational speed of spindle driver 101.

[0133] Each of these speed indications can be input to multiplexer 430,whose output is input to microprocessor 432 as the signal indicating therotational speed of spindle motor 101. Microprocessor 432 can choosethrough a select signal to multiplexer 430 which of these rotationalspeed measurements to use in a digital servo loop for controlling therotational speed of spindle driver 101.

[0134] Microprocessor 432 and DSP 416 output control efforts to driversthat affect the operation of drive 100 in response to the previouslydiscussed signals from actuator arm 104 and spindle driver 101. Acontrol effort from microprocessor 432 is output to spin control 456 toprovide a spin control signal to driver 340 (see FIG. 3A) forcontrolling spindle driver 101. A digital servo system executed onmicroprocessor 432 or DSP 416 is further discussed in the Spin MotorServo System disclosures. In some embodiments, as is further discussedbelow, microprocessor 432 outputs a coarse tracking control effort toserial interface 458.

[0135] In embodiments of drive 100 with a digital servo loop forcontrolling laser power, a signal from microprocessor 432 or DSP 416 isinput to a laser control digital to analog converter 460 to provide acontrol effort signal to the laser driver of laser servo 105 (see FIG.3A). A focus control signal can be output from either microprocessor 432or DSP 416 to a focus digital to analog converter 464 to provide a focuscontrol signal to power driver 340 (see FIG. 3A). A tracking controlsignal, which in some embodiments can be a fine tracking control effort,can be output from either microprocessor 432 or DSP 416 to a trackingdigital to analog converter 468 to provide a tracking control signal topower drivers 340. A diagnostic digital to analog converter 466 andother diagnostic functions, such as analog test bus 470, digital testbus 472, and diagnostic PWM's 474, may also be included. Further areference voltage generator 462 may be included to provide a referencevoltage to digital-to-analog converters 460, 464, 466, and 468.

[0136] Microprocessor 432 and DSP 416 can communicate through directconnection or through mailboxes 434. In some embodiments, DSP 416operates under instructions from microprocessor 432. DSP 416, forexample, may be set to perform tracking and focus servo functions whilemicroprocessor 432 provides oversight and data transfer to a hostcomputer or to buffer memory 320. Further, microprocessor 432 mayprovide error recovery and other functions. Embodiments of controlarchitectures are further discussed in the System Architecturedisclosures. DSP 416, in some embodiments, handles only tracking andfocus servo systems while microprocessor 432 handles all higher orderfunctions, including error recovery, user interface, track and focusservo-loop closings, data transport between optical media 102 and buffermemory 320, and data transfer between buffer memory 320 and a host, readand write operations, and operational calibration functions (includingsetting offset and gain values for offset 402-1 through 402-6 andamplifiers 404-1 through 404-6 and operational parameters for decimationfilters 414-1 through 414-6).

Tracking and Focus Servo Algorithms

[0137]FIGS. 5A and 5B together show a block diagram of an embodiment oftracking, focus and seek algorithms 500. Algorithms 500 shown in FIGS.5A and 5B can be, for example, primarily executed on DSP 416 of FIG. 4.In some embodiments, real-time tracking and focus algorithms areexecuted on DSP 416 whereas other functions, including calibration andhigh-level algorithm supervision, are executed on microprocessor 432. Insome embodiments, microprocessor 432 can also manage which algorithmsare executed on DSP 416. Algorithm 500 includes a focus servo algorithm501 and a tracking algorithm 502. Further algorithms include amulti-track seek algorithm 557 and a one-track jump algorithm 559.

[0138] Focus servo algorithm 501, as shown in FIGS. 5A and 5B, includes,when fully closed, summer 506, offset summer 507, FES gain 509, inversenon-linearity correction 511, cross-coupling summer 513, FES sampleintegrity test 515, low frequency integrator 516, phase lead 518, notchfilter 519, focus close summer 521, loop gain 524, and feed-forwardsummer 533. Similarly, tracking servo loop 502, when fully closed,includes summer 540, offset summer 541, TES gain 543, TES inversenon-linearity correction 546, TES sample integrity test 548, lowfrequency filter 549, phase lead 550, notch filters 551 and 553, andloop gain amplifier 564.

[0139] Further, algorithm 500 includes detector offset calibration 584and detector gain calibration 583. Along with other calibrationprocedures shown in algorithm 500, these calibrations are discussedfurther below.

[0140] As shown in block 503, digitized and filtered signals A_(f),E_(f), C_(f), B_(f), F_(f), and D_(f) from decimation filters 414-1through 414-6 as shown in FIG. 4. For purposes of discussion, signalsA_(f), E_(f), C_(f), B_(f), F_(f), and D_(f) have been relabeled insubsequent Figures to be A, E, C, B, F, and D, respectively. Block 504receives signals A, C, and E and calculates an FES₁ signal as

FES₁=(A+C−E)/(A+C+E)

[0141] as was previously discussed with FIG. 2J with the analog versionsof signals A, C, and E. Block 505 receives signals B, D, and F andcalculates an FES₂ signal according to

FES₂=(B+D−F)/(B+D+F)

[0142] as was previously discussed with FIG. 2K with the analog versionsof signals B, D, and F. Summer 506 calculates the differential FESsignal according to

FES=FES₁−FES₂

[0143] As was previously discussed, FIG. 2L shows the FES signal as afunction of distance between OPU 103 and optical media 102. Aspreviously discussed, in some embodiments further processing can beperformed on TES and FES signals, for example to reduce cross-talk.

[0144] The FES signal is input to offset adder 507, which adds an FESoffset from offset calibration 508. The best position on the FES curve(see FIG. 2L) around which a servo system should operate can bedifferent for the servo system than it is for read or write operations.In other words, optimum read operations may occur around a position onthe FES curve that differs from the optimum position utilized for bestservo operation. FES offset calibration 508, which inputs thepeak-to-peak tracking error signal TES P-P and a data jitter value andoutputs an FES offset value, is further discussed below.

[0145] The output signal from offset adder 507 is input to FES Gain 509.The gain of FES gain 509 is determined by FES gain calibration 510. Thegain of FES gain 509 is such that the output value of gain 509corresponds to particular amounts of focus displacement at focusactuator 206. Fixing the correlation of the magnitude of the outputsignal from gain 509 with particular physical displacements of OPU 103allows the setting of thresholds that determine whether or not focusloop 501 is sufficiently closed to transfer data. Although discussedfurther below, FES gain calibration 510 can determine an appropriatevalue of the gain for FES gain 509 by varying the distance between OPU103 and optical media 102 and monitoring the peak-to-peak value of theresulting FES signal. In some embodiments, the gain of FES gain 509 canbe fixed.

[0146] As a result of the calibrated gain of FES gain 509, the FESsignal output from FES gain 509 can have a set peak-to-peak value.Between the peaks of the amplified FES signal from FES gain 509 is anear linear region of operation. Focus servo algorithm 501 operates inthis region unless a shock sufficient to knock focus out of the linearregion is experienced. It is beneficial if, between separate drives andbetween different optical media 102 on drive 100, along with anydifferences in detectors and actuator response between drives, that theFES output from FES gain 509 be normalized. This allows for thresholdvalues independent of particular drive or particular optical media to beset based on the amplified FES to determine ability to read or write tooptical media 102. In some embodiments, for example, the peak-to-peakmotion of OPU 103 relative to optical media 102 may correspond to abouta 10 μm movement.

[0147] However, although the amplified FES output from FES gain 509 canbe normalized to a particular peak-to-peak value corresponding toparticular displacements of OPU 103 relative to optical media 102, theamplified FES output can be non-linear between those peaks. FES inversenon-linearity 511 operates to remove the potentially destabilizingeffects of non-linearity of the amplified FES. In some embodiments,calibration 512 may create a table of gains related to the slope of theFES as a function of the FES offset value. In that case, if a shockoccurs and the servo is on a different offset value of the FES curve,then FES inverse non-linearity 511 can obtain a linearizing gain valuefrom the table of gains. In that fashion, FES inverse non-linearity 511can help quickly react to a shock to recover focus. In some embodiments,the FES curve can be recorded and the gain of FES non-linearity 511 canbe set according to the recorded FES curve. In either case, the gainsetting of inverse non-linearity 511 is set depending on the FES offsetvoltage, which determines the point on the FES curve about which servosystem 501 is operating.

[0148] The output signal from FES inverse non-linearity 511 is input tocoupling summer 513. An estimate of the optical cross-coupling with acorresponding TES signal is subtracted from the FES at summer 513. Theestimated correction is determined by Tes-to-Fes Cross-Coupling Gain514. TES-to-FES cross-coupling gain 514 may, in some embodiments,determine the amount of TES to subtract in summer 513 from a ratioproduced by TES-to-FES Cross Talk Gain Calibration 579. As discussedfurther below, calibration 579 can insert a small test component (e.g.,a sine wave) to the tracking control effort signal and measure theeffects on the FES signal at the input of summer 513 in order todetermine the ratio used in cross-coupling gain 514.

[0149] Therefore, a certain percentage of the TES signal is subtractedfrom the FES signal in summer 513. In some embodiments, the particularpercentage (indicated by the gain of gain block 514) can be fixed. Insome embodiments, a TES-to-FES cross-talk gain calibration 579determines the gain of gain block 514. Cross-talk gain calibration 579is further discussed below. In some embodiments, the gain of gain block514 can be changed depending upon the type of media, e.g. writeable orpremastered, that OPU 103 is currently over.

[0150] The output signal from cross-talk summer 513 is input to FESsample integrity test 515. Sharp peaks may occur in the FES signal as aresult of many factors, including defects in optical media 102, dust,and mechanical shocks. These signals occur as a dramatic change from thetypical FES signal that has been observed at integrity test 515. In someembodiments, signals of this type may be on the order of 10 to 500microseconds in duration. In many instances, the resulting FES signalmay indicate an apparent acceleration of actuator arm 104 that isphysically impossible. It would be detrimental to overall operation ofdrive 100 for focus servo algorithm 501 to respond to such sporadicinputs since, if there is a response by focus servo algorithm 501,recovery to normal operation may take a considerable amount of time.Therefore, integrity test 515 attempts to detect such signals in the FESsignal and cause focus servo algorithm 501 to ignore it by filtering thesignal out.

[0151] Integrity test 515 inputs a defect signal, which can be thedefect signal output from disturbance detector 440 shown in FIG. 4.Essentially, upon receiving a defect signal, integrity test 515 createsa low-pass filtered version of the FES signal to substitute for thedefective FES signal. In some embodiments, a defect flag can be set eachtime this occurs so that error recovery can be initiated if too manydefects, resulting in filtered FES signals, are experienced. Use of thelow-pass filtered FES signal over a long period of time can causephase-margin problems in focus servo algorithm 501, which can affect thestability of drive 100.

[0152] In some embodiments, sample integrity test 515 may low-passfilter FES signal at its input and subtract the filtered FES signal fromthe received input FES signal. If a peak in the difference signalexceeds a threshold value, then the low-pass filtered FES signal isoutput from integrity test 515 instead of the input FES signal and adefect flag is set or a defect counter is incremented. The occurrence oftoo many defects in too short a time can be communicated to an errorrecovery algorithm. See the System Architecture Disclosures.

[0153] In some embodiments, the change in the FES signal betweenadjacent cycles can be monitored. If the change, measured by thedifference between the FES signal in the current cycle and the previouscycle, is greater than a threshold value, then the low-pass filtered FESsignal is output from integrity test 515 instead of the input FES signaland a defect flag can be set and the defect counter incremented.

[0154] In some embodiments, FES sample integrity test 515 may bedisabled. Disabling FES sample integrity test 515, in some embodiments,may occur during focus acquisition so that focus servo algorithm 501 canbetter respond to transient effects. In some embodiments, FES sampleintegrity test 515 may be disabled during multi-track seek algorithm 557and during one-track jump algorithm 559. In some embodiments, FES sampleintegrity test 515 may be disabled while track following during a readto write transition.

[0155] The output signal from FES sample integrity test 515 is input toTES OK detector 517. If a low pass filtered (e.g., 200 Hz 2^(nd) orderlow pass) version of the absolute value of the FES signal FES′ outputfrom integrity test 515 exceeds a TES OK threshold value, then atracking error signal TES can not be trusted. In reality, if the FESsignal deviates significantly from its best focus value, then the TESsignal can become small. A small TES signal indicates to tracking servoalgorithm 502 that tracking is good, which is not the case. Instead,focus has deviated so that tracking is no longer reliable. Under theseconditions, an error recovery algorithm can be initiated. See the SystemArchitecture Disclosures.

[0156] In some embodiments of the invention, the FES signal FES′ isinput to seek notch filter 590. Seek notch filter 590 is adjusted tofilter out signals at the track crossing frequency when a multi-trackseek operation is being performed. Even though there is a TES-FEScross-coupling correction at summer 513, not all of the TES signal willbe filtered out of the FES signal, especially during a multi-track seekoperation. Therefore, notch filter 590 can be enabled during amulti-track seek operation in order to help filter more of the TES-FEScross coupling from the FES signal. When not enabled, notch filter 590does not filter and the output signal from filter 590 matches the inputsignal to filter 590.

[0157] The FES signal output from notch filter 590 can be input to lowfrequency integrator 516. The low frequency integrator provides furthergain at low frequencies as opposed to high frequencies. Since theresponses to which focus actuator 206 should respond, as discussedabove, occur at low frequencies, there is a large incentive in focusservo loop 501 to increase the gain at low frequencies and placeemphasis on the servo response at those frequencies. In order to furtheremphasis the low frequencies, in some embodiments low frequencyintegrator 516 can be a 2^(nd) Order low frequency integrator.Integrator 516 provides additional error rejection capability for lowfrequency disturbances such as DC bias, external shock and vibration. Anexample transfer function for low frequency integrator 516 is shown inFIG. 5C. Low frequency integrator 516, for example, can be particularlysensitive to frequencies less than about 100 Hz in order to boost servoresponse to frequencies less than 100 Hz.

[0158] The output signal from integrator 516 is input to phase lead 518.Phase lead 518 provides phase margin or damping to the system forimproved stability and transient response. In some embodiments, forexample, phase lead 518 can be sensitive to frequencies greater thanabout 500 Hz. Again, in some embodiments of the invention, phase lead518 can be a second order phase lead. Further, in some embodimentsintegrator 516 can be disabled during focus acquisition in order toallow focus servo system algorithm 501 to better respond to transienteffects during a focus acquisition procedure. An example transferfunction for phase lead 518 is shown in FIG. 5D.

[0159] In some embodiments, low frequency integrator 516 and phase leadcompensation 518 are accomplished with second order filters instead offirst order filters. A second order low frequency integrator providesmore low frequency gain, providing better error rejection, than a firstorder integrator. Additionally, a second order phase lead compensatorprovides increased phase advance or phase margin at the servo open loopbandwidth than that of a first order phase lead compensator. The secondorder phase lead compensator also causes less high frequencyamplification than that of a first order phase lead for the same amountof phase advance at the crossover.

[0160] The output signal from phase lead 518 can be input to a notchfilter 519. Notch filter 519 filters out signals at frequencies that, ifacted upon by focus servo algorithm 501, would excite mechanicalresonances in drive 100, for example in actuator arm 104. In general,notch filter 519 can include any number of filters to remove particularfrequencies from the FES signal output from phase lead 518. In someembodiments, notch filter 519 filters out any signal that can excite amechanical resonance of actuator arm 104 that occurs at around 6 KHz insome embodiments of actuator arm 104.

[0161] The output signal from notch filter 519 is input to summer 521.Summer 521 further receives a signal from focus close 535. Focus close535, during operation, provides a bias control effort to servo loop 501.In some embodiments, focus close 535 provides a focus acquire signalthat is summed with the output signal from notch filter 519. In someembodiments, the focus acquire signal operates through focus actuator206 to first move OPU 103 away from optical disk 102 and then to moveOPU 103 back towards optical disk 102 until an FES signal is acquired,after which the focus acquire signal is held constant. When the focusacquire signal is held constant at the bias control effort, servoalgorithm 501 operates with the FES signal measured from the A, C, E, B,D, and F values and is therefore a closed loop (with a variation in theFES signal resulting in a corresponding correction in the focus controlthat is applied to focus actuator 206).

[0162] The output signal from summer 521, then, is input to loop gain522. Loop gain 522 applies a gain designed to set the open-loopbandwidth of servo algorithm 501 to be a particular amount. For example,in some embodiments the open-loop bandwidth is set at about 1.5 kHz,which means that the open loop frequency response of the entire servoloop (including OPU positioner 104, signal processing, and algorithm501) is OdB at 1.5 kHz. Although focus loop gain calibration 522 isfurther discussed below., in essence a sine wave generated in sine wavegenerator 528 is input to summer 523, resulting in a modulation of focuscontrol which translates into a modulation of the measured FES signal.The resulting response in the signal from summer 521 is monitored bydiscrete Fourier transform (DFT) 527, and DFT 525 in combination withgain calibration 526 in order to set the gain of loop gain amplifier524. In some embodiments where the transfer function at 1.5 kHz shouldbe unity, the sine wave generator provides a 1.5 kHz sine wave functionto summer 523 and gain calibration 526 set the gain of loop gain 524 sothat the overall gain of the 1.5 kHz component of the signal output fromsummer 521 is equal to the overall gain of the 1.5 KHz component of thesignal output from summer 523.

[0163] The output signal from loop gain 524 is input to multiplexer 531,along with a low-pass filtered version formed in filter 529 and a signalfrom sample and hold (S/H) 530. During normal operation, multiplexer 531is set to output the output signal from loop gain 524. Although much ofthe optical cross-talk is canceled from the control effort signal atsummer 513, there is still enough cross talk so that, while OPU 103 iscrossing tracks on optical media 102, a track crossing component of thecontrol effort will appear in the output signal of loop gain 524. Insome embodiments, seek operations are accomplished at fairly high rates,resulting in a track crossing signal of the order of a few kHz.Therefore, during a seek operation a low-pass filtered version of theoutput signal from loop gain 524 can be substituted for the signal fromloop gain 524. In some embodiments, the output signal from a sample andhold (S/H) 530 circuit can be substituted for the signal from loop gain524 by multiplexer 531. The effects of changing FES as OPU 103 passesover multiple tracks can then be prevented from translating into acorresponding movement of OPU 103.

[0164] In a one-track jump operation, there is a similar concern abouteffects on the FES signal from crossing tracks (i.e., TES-FEScrosstalk). In some embodiments, in a one-track jump, the output signalfrom sample and hold (S/H) 530 is output from multiplexer 531. Sampleand hold (S/H) 530 holds the output signal to match that of previousoutput signals so that the resulting control effort is simply heldconstant through the one-track jump operation.

[0165] The output signal from multiplexer 531 is input to summer 533.The output signal from summer 533 is, then, the control effort signalthat is input to focus DAC 464 (FIG. 4) from DSP 416 and then to powerdriver 340 to result in a current being applied to focus actuator 206 toprovide focus. In summer 533, the output signal from multiplexer 531 issummed with an output signal from feed-forward loop 532. Feed-forwardloop 532 inputs the output signal from multiplexer 531 and attempts topredict any regularly occurring motion of OPU 103 relative to opticalmedia 102. These motions occur, for example, because optical media 102is not flat and the surface of optical media 102 will vary in a regularway as optical media 102 is spun. As a result, left alone, there will bea FES generated having the same harmonic as the rotational rate ofoptical media 102. Feed-forward loop 532 provides these harmonics tosummer 533 so that the control effort includes these regular harmonics.In that case, the FES signal calculated from signals A, C, E, B, F, Dwill not include these regular harmonics. In some embodiments,feed-forward loop 532 responds to multiple harmonics of any such regularmotion of OPU 103 so that none of the harmonics are included in thecalculated FES signal.

[0166] In order to determine if the focus is OK, a sum of all of thedetector signals A, C, E, B, D and F is calculated in summer 534 and theresultant sum is input to Focus OK block 536. Focus OK block 536compares the overall sum with a focus threshold value generated by FESGain calibration 510 and, if the sum is greater than the focusthreshold, indicates a focus OK condition. If, however, the sum is lessthan the focus threshold, then a focus open signal is generated by focusOK block 536. In some embodiments, focus OK block 536 may indicate anopen focus condition only after the sum signal has dropped below thefocus threshold for a certain period of time. This will prevent a defectsituation (e.g., a dust particle) from causing servo algorithm 501 tolose (i.e., open) focus.

[0167] The output signal from summer 534 is also input to defectdetector 591. Defect detector 591 monitors a high-pass filtered sumsignal to identify the presence of media defects. In some embodiments,if the high-pass filtered sum signal exceeds a threshold value then thepresence of a defect is indicated. In some embodiments, defect detector591 can determine whether or not changes in the sum signal from summer534 are the result of changes in laser power (for example in transitionsfrom read to write or write to read or in spiraling over previouslywritten data) as media defects. In some embodiments, defect detector 591will “time-out” if the defect appears to remain present for a longperiod of time, which under that condition may indicate other than amedia defect.

[0168] In some embodiments, defect detector 591 detects defects bydetecting sudden changes in the sum signal. A change in laser power canresult in a sudden changes in the sum signal which can be falselyidentified as a defect. In some embodiments, a laser servo controllercan inform defect detector 591 of changes in laser power. Once defectdetector 591 is notified of a change, then defect detector can delay fora time period (for example about 5 ms) to allow the sum signal andtransients from a sum signal low pass filter in defect detector 591 tosettle before proceeding to detect detects. Notification of defectdetector 591 before a laser power change can reduce the risk of falselyidentifying a defect. In some embodiments, defect detector 591, whichcan be executed on DSP 416, can monitor the focus sum threshold value,which can be changed in by microprocessor 432 when laser power ischanged. Defect detector 591 can then by notified of changes in laserpower by the change in focus sum threshold value.

[0169] Additionally, the sum signal can change when crossing media types(e.g., from premastered to writeable or from writeable to premastered).In some embodiments, multi-track seek algorithm 557 knows when aboundary crossing will occur. In some embodiments, multi-track seekalgorithm 557 can inform defect detector 591 when a boundary is crossedso that a false defect detection at a boundary crossing does not occur.In some embodiments, the defect threshold value, the threshold valueagainst which the sum signal is compared to detect defects, can be setlarge enough to not respond to changes in reflectivity associated with amedia type boundary change. However, if the defect threshold value isset too high defects may not be detected.

[0170] Sliding Notch Filter 595 can reduce the effects of opticalcross-talk (TES into FES) during multi-track seek operations.Multi-track seek controller 557 can be a velocity controlled servocontroller. Sliding notch filter 595 can track the seek referencevelocity of multi-track seek controller 557. For example, the maximumreference velocity could be 10 kHz and the minimum reference velocitycould be 2 kHz. Sliding notch filter 595 can vary it's center frequencyfrom 10 kHz to 2 kHz as a function of the seek reference velocitymulti-track seek controller 557.

[0171] Tracking servo algorithm 502, in many respects, is similar inoperation to focus servo algorithm 501. In some embodiments, trackingservo algorithm 502, when closed, inputs detector signals A, C, B, and Dand calculates a tracking error signal TES from which a tracking controleffort is determined. In some embodiments a coarse tracking controleffort, which is output from loop gain calibration 562, and a coarsetracking control effort, which is output from feedforward control 585,can be output.

[0172] Detector signals A and C are input to block 538, which calculatesa tracking error signals TES₁ according to

TES₁=(A−C)/(A+C)

[0173] such as is described with FIG. 2P. Detector signals B and D areinput to block 539, which calculates TES₂ according to

TES₂=(B−D)/(B+D)

[0174] such as described with FIG. 2Q. The difference between TES₁ andTES₂ is calculated in summer 540 to form a TES input signal, as isdescribed with FIG. 2R. The TES input signal responds to variation inthe tracking motion of OPU 103 (as controlled by tracking actuator 201)as discussed above with the analog versions of signals A, C, E, B, D,and F, for example, with FIGS. 2M through 2R. In some embodiments,further processing of the TES signal may be performed, for example toreduce cross-talk.

[0175] The TES signal output from summer 540 is input to summer 541,where it is summed with an offset value. The offset value is determinedby TES offset calibration 542. The output signal from offset summer 541is input to TES gain 543, which calibrates the peak-to-peak value of theTES signal in accordance with a TES gain calibration algorithm 544. Asdiscussed above, the TES signal as a function of tracking position is asine wave. As discussed below, in some embodiments the TES offset valuecan be determined to be the center point between the maximum and minimumpeaks of the TES sine wave. Additionally, in some embodiments the TESoffset value can be affected by a determination of the optimum value ofthe TES offset value for data reads or writes and may vary for differingtracking positions across optical media 102. In some embodiments, theTES gain calibration is set so that the peak-to-peak value of theresulting TES signal output from TES gain is at a preset peak-to-peakvalue. The preset peak-to-peak value is selected to provide the bestdynamic range over the range of tracking motion of OPU 103.

[0176] Information regarding the peak-to-peak value of the TES signal asa function of position on optical media 102 can be determined in TES P-P545. In an open tracking situation, the TES signal varies through itsrange of motions as tracks are crossed by OPU 103. TES P-P 545, in someembodiments, records the highest and lowest values of the TES signal asthe peak-to-peak values. In some embodiments, an average of the highestand lowest values of the TES signal is recorded as the peak-to-peakvalues. The peak-to-peak values can be input to Offset calibration 542which calculates the center point and gain calibration 544, whichcalculates the gain required to adjust the peak-to-peak values to thepreset value.

[0177] The TES signal output from offset 541 is input to TES gain 543.TES gain 543 can, in some embodiments, be calibrated by TES offsetcalibration 542. Calibration algorithms, such as TES offset calibration542, are further described below.

[0178] The TES signal output from TES gain 543 is input to TES inversenon-linearity 546. TES inverse non-linearity 546 operates to linearizethe TES signal around the operating point determined by the TES offset,as was discussed above with respect to FES inverse non-linearity 511.Calibration 547 can calculate the gain of TES non-linearity 546 forvarious values of TES offset to linearize the TES signal as a functionof position about the operating point.

[0179] The output signal from TES inverse non-linearity 546 is input toTES sample integrity test 548. TES sample integrity test 548 operateswith the TES signal in much the same fashion as FES sample integritytest 515 operates with the FES signal, which is discussed above. In someembodiments, TES sample integrity test 548 can be enabled with anenablement signal. When TES sample integrity test 548 is not enabled,then the output signal from TES sample integrity test 548 is the same asthe input signal to TES sample integrity test 548.

[0180] The input signal to TES sample integrity test 548 and the inputsignal to FES sample integrity test 515 and a defect signal produced bydefect detector 591 are input to write abort algorithm 537, whichdetermines whether, in a write operation, the write should be aborted.If it appears from FES or TES that TES or FES is too large (i.e., one ofTES and FES has exceeded a threshold limit), then write abort 537 abortsa write operation to the optical media 102 by providing an abort writeflag. However, if TES or FES exceeds the threshold limits and defectdetector 591 indicates a defect, the write is not aborted. In someembodiments, low pass filtered FES and TES values are utilized todetermine whether FES or TES are too large. Low pass filtered FES andTES values can essentially include the DC components of the FES and TESsignals. A programmable number N, for example 2, consecutive sampleswith TES or FES above limits and a defect indicated are allowed beforewrite abort 537 aborts a write operation. Aborting the write can preventdamage to optical media 102 due to the high power of laser 218, whichcrystallizes the amorphous material on the writeable portion of opticalmedia 102. Further, damage to adjacent track data can also be prevented.

[0181] The output signal from TES sample integrity test, TES', is, in aclosed tracking situation, input to low frequency integrator 549 andthen to phase lead 550. Low frequency integrator 549 and phase lead 550operate similarly to low frequency integrator 516 and phase lead 518 offocus servo algorithm 501. Again, in order to provide better response tolow frequency portions of TES, low frequency integrator 516 and phaselead 518 can be second order filters. As discussed previously, a secondorder low frequency integrator provides more low frequency gain,providing better error rejection, than a first order integrator.Additionally, a second order phase lead compensator provides increasedphase advance or phase margin at the servo open loop bandwidth than thatof a first order phase lead compensator. The second order phase leadcompensator also causes less high frequency amplification than that of afirst order phase lead for the same amount of phase advance at thecrossover.

[0182] The output signal from phase lead 550 is input to notch filter551. Notch filter 551 can be calibrated by notch calibration 552. Again,notch filter 551 prevents control efforts having frequencies that excitemechanical resonances in actuator arm 104. These mechanical resonancescan be well known in nature (depending on the structure of actuator arm104) but may vary slightly between different drives. The output signalfrom notch filter 551 can be input to a second notch filter 553 in orderthat fixed and known resonances can be filtered. Notch filter 551 andnotch filter 553 can each include multiple notch filters.

[0183] In some embodiments, the output signal from notch filter 553 isinput to a retro-rocket loop gain amplifier 830. Retro rocket 830provides additional gain to tracking servo loop 501 after execution of amulti-track seek operation in order to more aggressively close trackingon a target track. Retro rocket 830 is enabled by multi-track seekcontroller 557.

[0184] In a closed-tracking mode, switch 556 is closed and the outputsignal from notch filter 553 is input to multiplexer 558. Again, in aclosed tracking mode, multiplexer 558 provides the output signal fromnotch filter 553 to loop gain calibration 562. As discussed above withrespect to focus loop gain calibration 522, loop gain calibration 562arranges that the frequency response at a selected frequency is OdB. Todo that, a sine wave generated in generator 568 is added to the controleffort in summer 563 and the response in input signal to gaincalibration 562 is monitored. The input signal is provided throughDiscrete Fourier Transform (DFT) 567 to gain calibration 566, along withthe output signal from summer 563 processed through DFT 565. Gaincalculation 566, then, sets the gain of loop gain 564 so that the openloop gain has 0 dB of attenuation at that frequency. The bandwidth setby loop gain calibration 562 may differ from the bandwidth set by focusloop gain calibration 522.

[0185] Switch 556 is closed by close tracking algorithm 555. Whentracking is open, the TES signal is a sine wave as tracks pass below OPU103. The period of the sine wave represents the time between trackcrossings. Tracking can be closed near, for example, the positivesloping zero-crossing of the TES versus position curve (see FIG. 2R). Ifa track closing is attempted at a zero-crossing with the improper slope,tracking servo algorithm 502 will operate to push OPU 103 into aposition at the zero-crossing with the proper slope.

[0186] In some embodiments, TZC detector 554 receives the TES' signalfrom TES sample integrity test 548 and determines the trackzero-crossings TZC and the TZC period, which indicates how fast tracksare crossing under OPU 103. In some embodiments, TZC can be input fromtracking crossing detector 454 and that TZC value can be utilized tocompute the TZC period. If the track crossings are at too high afrequency, then tracking algorithm 502 may be unable to acquire trackingon a track. However, in another part of the rotation of optical media102 the track crossing frequency will become lower, providing anopportunity to acquire tracking. In some embodiments, close trackingalgorithm 555 can reduce the angular speed of spin motor 101 if thetrack crossing frequency is too high.

[0187] Therefore, when close tracking algorithm 555 is commanded toclose tracking, close tracking algorithm 555 monitors the TZC periodand, when the TZC period gets high enough (i.e., the frequency of trackcrossings gets low enough), tracking algorithm 555 closes switch 556 toclose tracking servo loop algorithm 502 to operate closed loop on atrack. However, there can be large transients when switch 556 is closedbecause OPU 103 can have some initial velocity with respect to the trackwhen switch 556 is closed. Therefore, the lower the frequency ofcrossing (indicating a lower speed of OPU 103 with respect to thetracks), the lower the transients caused by closing switch 556. Priorand during closing of switch 556, the low frequency integrator 549 isdisabled by a enable signal from close tracking algorithm 555.

[0188] In some embodiments, the output signal from loop gain 564provides a fine control effort. In some embodiments, tracking DAC 468(FIG. 4) is an 8-bit digital-to-analog converter. Tracking actuator 201,however, needs to move OPU 103 from the inner diameter (ID) of opticalmedia 102 to the outer diameter (OD) of optical media 102. Therefore,although actuator arm 104 must move OPU 103 from ID to OD, whiletracking is closed small motions of OPU 103 around the tracking positionare required. For example, in some embodiments when tracking is closedOPU 103 moves in the range of approximately ±70 nm around a centralposition. Further, in some embodiments a full stroke from ID to OD isapproximately ¼ inch to a ½ inch. In addition to the large dynamic rangerequired to move OPU 103 from ID to OD on optical media 102, there isalso a spring force in the mounting of spindle 203 of actuator arm 104to overcome.

[0189] Therefore, in some embodiments of the invention a second DACconverter can be utilized as a coarse actuator control while the controleffort from loop gain 564 can be utilized as a fine actuator control.The tracking control effort signal output from loop gain 564, then, isinput to tracking DAC 468 (FIG. 4). Tracking DAC 468 can have any numberof bits of accuracy, but in some embodiments includes an 8-bit digitalto analog converter.

[0190] In some embodiments, a coarse tracking control effort isgenerated by bias feedforward control 585. The coarse tracking controleffort generated by bias feedforward control 585 can be thelow-frequency component of the tracking control effort produced by loopgain 564. The coarse tracking control effort, then, can be communicatedto microprocessor 432, which can then transfer the coarse control effortto power driver 340 (FIG. 3A) through serial interface 458. A seconddigital-to-analog converter in power driver 340, in some embodimentshaving an accuracy of 14 bits, receives the coarse control effort frommicroprocessor 432 through serial interface 458. In power drive 340, theanalog course control effort is then summed with the analog fine controleffort from DAC 468 to provide the whole tracking control current totracking actuator 201. Therefore, microprocessor 432 can determine thelow frequency component of the tracking control effort in order to biastracking actuator 201 while DSP 416, executing tracking servo algorithm502, determines the fine tracking control effort to hold OPU 103 ontrack.

[0191] In some embodiments, the output signal from loop gain 564 isinput to anti-skate algorithm 593. Anti-skate algorithm 593 receives adirection signal from direction detector 592 and an anti-skate enablesignal from tracking skate detector 561. Anti-skate algorithm 593, whenenabled, determines which TES slope is stable and which is unstable. Thestable slope will be different for the two opposite directions of motionof OPU 103 relative to optical media 102. For example, if a positivesloping TES signal is stable when OPU 103 is traveling from the innerdiameter (ID) to the outer diameter (OD), the negative sloping TESsignal is stable when OPU 103 is traveling from the OD to the ID.Anti-skate algorithm 593, then, prevents tracking control loop 502 fromclosing on an unstable slope, which can prevent further skating fromattempting to close on the unstable slope. During periods when thetracking error signal indicates an unstable slope, a substitute trackingcontrol effort can be substituted for the tracking control effortreceived from tracking servo system 502. Anti-skate algorithm 593 allowstracking control algorithm 502 to more easily close onto a track once asignificant disturbance has caused the tracking servo to slide acrossseveral tracks (i.e. skate).

[0192] Bias control 585 receives the control effort signal from loopgain 564 through anti-skate algorithm 502. Low pass filter 569, whichcan be a 200 Hz second order filter, receives the tracking controleffort and passes only the low frequency component. The sign of thesignal output from low pass filter 569 is detected in sign 570. The signadds a set amount (for example +1, 0, or −1) to a track and hold circuitthat includes summer 574 and feedback delay 575. With 0 inputs to summer574, the output signal from summer 574 will be the last output signalreceived, as is stored in delay 575. Sign 570, then, determines whetherto increase the bias value of the coarse control effort or decrease thebias value of the coarse control effort. Since the decision to increaseor decrease the coarse control effort occurs only during an interruptcycle of microprocessor 432, and since a single increment or decrementis made per cycle, the course control effort resulting from bias forwardcontrol 585 varies very slowly (for example, one increment every 2 ms).

[0193] In operations, bias control 585 essentially removes the lowfrequency component of the fine tracking control effort output from loopgain 564 by transferring the low frequency control effort to coarsecontrol effort output from bias control 585. A constant control effortappearing on the fine tracking control effort, for example, willeventually be totally transferred to the coarse tracking control effortoutput from bias control 585. However, if the interaction between thefine tracking control effort and the coarse tracking control effort istoo fast, there can be stability problems. Therefore, there is incentiveto make bias control 585 respond slowly to changes in the low frequencycomponent of the tracking control effort output from loop gain 564. Theincrementing or decrementing of the coarse control effort output frombias control 585 occurs during the regular interrupt time (Ts) foroperating microprocessor 432, which can in some embodiments be about 2milliseconds.

[0194] In a closed tracking mode, the coarse control effort signaloutput from summer 578 changes very slowly. However, during seekoperations there is a need to change the coarse control effort signalmuch more quickly. Therefore, during seek operations, the output signalfrom low pass filter 569 is further filtered through low pass filter571. A portion (indicated by K multiplier in block 576) is added insummer 574 to the coarse control effort and to summer 578, whose outputis the coarse control effort. Therefore, during seek operations thecoarse control effort output from bias control 585 can change quickly.Low pass filter 571 allows frequencies low enough (e.g., less than about20 Hz) to allow the seek control effort to increase the coarse controleffort faster than the incremental changes allowed by switch 573 but isof low enough frequency that other disturbances do not affect the coarsecontrol effort output by summer 578.

[0195] Additionally, the output signal from low pass filter 569 is inputto off-disk detection algorithm 572, which monitors very low frequencycomponents. Since very low frequency components of the TES are amplifieda great deal through integrator 549 and phase lead 550, an essentiallyDC component of TES will have a large gain and, therefore, will be alarge component of the tracking control effort output from loop gain564. This low frequency component is not filtered by low-pass filter 569and, therefore, is input to off-disk detection algorithm 572. If a largeDC signal is observed over a period of time, off-disk detectionalgorithm 572 concludes that OPU 103 is outside of the operational rangeof optical media 102 and provides an error message to microprocessor432. Microprocessor 432, as described in the System Architecturedisclosures, then takes the appropriate error recovery steps.

[0196] In some embodiments, a calibrated tracking feed-forward control579 can also be included. Feed-forward control 579 can determine anyregular variations in the tracking control effort produced by loop gain564 and insert a corresponding harmonic effort into the tracking controleffort in order to anticipate the required motion of OPU 103. Thoseharmonics, then, would be subtracted from the TES.

[0197] When close tracking algorithm 555 closes tracking, in someembodiments integrator 549 and sample integrity test 548 may be disabledwhen switch 556 is first closed. This will increase the damping, at thecost of reduced low frequency gain, in tracking servo loop algorithm502. Once switch 556 is closed, close tracking algorithm 555 may waitsome time for any transient effects to decay before enabling integrator549 and then enabling sample integrity test 548. In other words, beforethe low frequency components of TES are boosted by integrator 549, servoloop algorithm 502 and actuator arm 104 have settled close to thedesired tracking position.

[0198] The TES' signal from sample integrity test 548 can also be inputto multi-track seek controller 557, one track jump control 559, andtracking skate detector 561. Multi-track seek controller 557, in amulti-track seek operation, supplies a control effort to multiplexer 558which, when selected, causes actuator arm 104 to move OPU 103 near to atarget track on optical media 102. After OPU 103 is at or near thetarget track, then close tracking algorithm 555 can be activated toclose tracking at or near the target track. One track jump algorithm559, which can be calibrated by a calibration algorithm 560, outputs acontrol effort signal to multiplexer 558 which, when selected, moves OPU103 by one track. In some embodiments, a large motion of OPU 103 can beundertaken by multi-track seek controller 557 and then one track jumpcontrol 559 can operate to move OPU 103 closer to the target trackbefore tracking is closed by close tracking algorithm 555. Trackingskate detector 561 monitors FES' and indicates when tracking has beenopened. If tracking skate detector 561 indicates an open trackingcondition, then tracking may need to be reacquired. Furthermore,tracking skate detector 561 enables anti-skate algorithm 593. A signalcan be sent to microprocessor 432 so that microprocessor 432 can executeerror recovery algorithms, which in this case may involve reacquiringtracking long enough to determine the position of OPU 103 and thenperforming a seek operation to move OPU 103 to the selected track andreacquiring tracking at the selected track. See the System ArchitectureDisclosures.

[0199]FIGS. 5E and 5F show an embodiment of tracking skate detector 561.As shown in FIG. 5E and 5B, tracking skate detector 561 receives theTES' signal from TES sample integrity test 548. As shown in FIG. 5F, asOPU 103 moves across tracks the TES' signal shows a sinusoidal signal.The absolute value of the TES' signal is calculated in block 594. Theoutput signal from absolute value block 594 is then input to low passfilter 595. In effect, low pass filter 595 can act as an integrator. Theoutput signal from low pass filter 595 is input to compare block 598where it is compared with an anti-skate threshold. The output signalfrom compare block 598 is input to threshold counter 599. If the outputsignal from low pass filter 595 exceeds the anti-skate threshold morethan a maximum number of clock cycles, then counter 599 sets the enableanti-skate flag, enabling anti-skate algorithm 593.

[0200] The output signal from low pass filter 595 is also input tocompare block 596. Compare block 596 compares the output signal from lowpass filter 595 with a skate threshold, which is typically larger thanthe anti-skate threshold. The output signal from compare block 596 isinput to counter 597. If the skate threshold is exceeded for a maximumnumber of cycles, then counter 597 outputs a skate detected flag. Theskate detected flag can then indicate that tracking is open.

[0201]FIG. 5G shows an embodiment of direction sensor 592. Directionsensor 592 determines the direction that optical pick-up unit 103 istraveling radially across the surface of optical pick-up unit 103.Summer 5001 sums the optical signals from outside elements of detectors225 and 226 (FIG. 2D), elements 231, 233, 234 and 236, to form adirection sum signal. In some elements, more or less than two detectorsare including in optical pick-up unit 103. The direction sum signal fromsummer 5001 includes both DC and AC components. The DC component of thedirection sum signal represents the laser intensity of laser 218. The ACcomponent of the direction sum signal is dominated by a quadraturesignal, which looks similar to TES when crossing tracks except that itis 90 degrees out of phase with the TES. In some embodiments, forexample, the direction sum signal can be 90 degrees phase advanced whentraveling from the inner diameter (ID) to the outer diameter (OD) ofoptical media 102 (FIG. 1B) and 90 degrees phase lagged when travelingfrom OD to ID of optical media 102.

[0202] The direction sum signal is input to sample and hold 5002 whilethe TES, for example from the output signal from summer 541, is input tosample and hold 5003. Media defects on optical media 102 can causeerroneous direction sum signals and TES signals, therefore the Sampleand Hold S/H functions 5002 and 5003 hold the high pass filter inputsignals constant during the presence of a media defect, indicated by thedefect signal from defect detector 591.

[0203] The output signals from sample and holds 5002 and 5003 are inputto high pass filters 5004 and 5005, respectively. The disk reflectivityof optical media 102 varies as a function of disk angular orientationresulting in an undesirable AC signal at the first harmonic of therotation frequency of optical media 102. The High Pass filter cutofffrequency of filters 5004 and 5005, then, can attenuate the firstharmonic reflectivity variation signal. The output signal from High Passfilter 5004, SumHp, is an AC signal representing the quadraturecomponent from the sum signal. Block 5006 converts the analog SumHpsignal into a digital logic signal SumHpD, depending on whether SumHp isgreater than or less than zero. High Pass Filter 5004 introduced a phaseshift into the resulting SumHpD. High Pass Filter 5005 introduces thesame phase shift into the TES in order to form a TESHpD signal, whichthen has a matching phase shift. Similarly, block 5007 converts theTESHpD signal into a logic signal by comparing the TESHpD signal withzero. Logic blocks 5007, 5008, 5009, 5010 and 5011 together perform thefollowing logic function:

Direction'=(TESHpD AND {overscore (SumHpD)}) OR ({overscore (TESHpD)}ANDSumHpD)

[0204] The polarity of the direction sensor changes between Mastered andWrite-able media. Inverter 5012 inverts Direction' and switch 5013outputs a direction signal from the output signal of inverter 5012 orfrom direction', depending on whether OPU 103 is over mastered orwrite-able media.

[0205]FIG. 6 shows an embodiment of a close tracking algorithm 555 (FIG.5B). Close tracking algorithm 555 closes tracking servo algorithm 502and therefore acquires tracking. In step 601, algorithm 555 receives acommand to close tracking. The close tracking command can originate frommicroprocessor 432 or from another algorithm executing in DSP 416. Oncethe close tracking command is received, algorithm 555 proceeds to step611

[0206] In step 611, the TES gain is set based on the peak-to-peak valueof the TES signal. In some embodiments, the TES gain can be set forgroove crossings or bumps. From step 611, algorithm 555 proceeds to step602.

[0207] In step 602, algorithm 555 determines the TZC period in order todetermine the track crossing speed, indicating the relative velocitybetween OPU 103 and the tracks on optical media 102. The track crossingspeed is related to the period of track crossing parameter TZC, whichcan be determined from TZC detector 554 or can be calculated from TES'.

[0208] After the track crossing speed is determined in step 602,algorithm 555 checks for a time-out condition in step 603 by determiningwhether too much time has passed since the close tracking command wasreceived in step 601. If too much time has passed, a microprocessortime-out flag is set and microprocessor 432 proceeds to an errorrecovery routine. Otherwise, algorithm 555 proceeds to step 604.

[0209] Step 604 determines if the track crossing rate is too high toclose tracking. Step 604 can determine if the track crossing rate is toohigh, for example, by comparing the TZC period with a track closethreshold. If the threshold is not exceeded, then the track crossingrate is too high and algorithm 555 returns to step 602. If the trackcrossing rate is low enough, then algorithm 555 continues to step 605.

[0210] In step 605, close tracking algorithm 555 closes switch 556,thereby closing the tracking servo loop. When switch 556 is firstclosed, integrator 549 and integrity test 548 are disabled to allowbetter response of the tracking servo loop while transient effectsdecay. Once switch 556 is closed, algorithm 555 proceeds to step 606.

[0211] In step 606, algorithm 555 delays long enough for transienteffects from closing switch 556 to decay. Once a particular delay timeperiod has elapsed, algorithm 555 proceeds to step 607 where integrator549 is enabled. Enabling integrator 549 introduces a new set oftransient effects. Therefore, once integrator 549 is enabled, algorithm555 proceeds to step 608, which waits for another delay time. Once thesecond delay time has elapsed, algorithm 555 proceeds to step 609 whereTES sample integrity test 548 is enabled.

[0212] Once step 609 is complete, algorithm 555 proceeds to stop 610where a tracking closed flag can be sent to either microprocessor 432 orDSP 416, depending on where the original close tracking commandoriginated. In some embodiments of the invention, algorithm 555 isperformed as a join effort between both microprocessor 432 and DSP 416.For example, microprocessor 432 may command DSP 416 to close loop instep 601. DSP 416 receives TZC period in step 602 and checks to see ifthe TZC is below a TZC threshold in step 604. Meanwhile, microprocessor432 begins a time-out clock. If DSP 416 has not closed switch 556 withinthe time-out period, then microprocessor 432 proceeds to error recovery.Once switch 556 is closed, DSP 416 will not proceed on this algorithmuntil, in step 607, microprocessor 432 tells DSP 416 to enableintegrator 549. Microprocessor 432 controls the relative timing, whilethe DSP 416 is slaved and only responds to commands from microprocessor432. Further, once integrator 549 is enabled in step 607, microprocessor432 then can tell DSP 419 to enable sample integrity test 548. In someembodiments, without commands from microprocessor 432, DSP 419 will notchange state.

[0213]FIG. 7A shows a block diagram of an embodiment of focus closealgorithm 535. Focus close algorithm 535 asserts control efforts ontothe focus control effort through summer 521. In some embodiments, summer521 may be replaced with a switch or multiplexer circuit that chooses acontrol effort originating from focus close algorithm 535 or from notchfilter 519.

[0214] Algorithm 535, in some embodiments, starts with a control effortso that OPU 103 is positioned away from optical media 102 (i.e., thedistance between OPU 103 and optical media 102 is larger than the focusdistance). Algorithm 535 then generates a control effort to move OPU 103closer to optical media 102 until the control effort is appropriate fora focus distance. Once OPU 103 is near the focus distance, thenalgorithm 535 holds its contribution to the control effort constantwhile the focus servo loop 501 generates the additional focus controleffort required to maintain closed loop focus.

[0215] In step 701, a focus acquire flag is set. The focus acquire flagcan be set by a routine executing in microprocessor 432 or in DSP 416.In step 703, algorithm 535 determines whether the actuator is positionedappropriately to start a focus acquisition procedure. This can be testedby setting a range of values for the current focus control effort or bycomparing with a threshold value for the focus control effort. In someembodiments, the current in focus actuator 206 is zero and algorithm 535needs to push OPU 103 away from optical media 102.

[0216] If the control effort for focus actuator 206 is not positionedappropriately, then algorithm 535 must generate a focus control effortappropriate to move OPU 103 to an acceptable starting point. Inaddition, algorithm 535 should provide a control effort that moves OPU103 in such a way as to not excite mechanical resonances in actuator arm104. For example, if a focus control effort profile is generated byalgorithm 535 that simply sets the focus control effort to a valuecalculated to be the value at the acquisition starting position, manymechanical resonances are likely to be excited in actuator arm 104.Should mechanical resonances in actuator arm 104 become excited, theremay be transient motions generated with large decay times, increasingsignificantly the amount of time required for focus acquisition. In someembodiments, in step 704 algorithm 535 generates a sinusoidal startingfocus control effort profile which moves OPU 103 to an acquisitionstarting position in a smooth fashion.

[0217]FIG. 7B shows an example of a starting focus control effortprofile generated in step 704. Step 704 generates a sine wave with onepeak being at the current focus control effort (indicating the currentposition of OPU 103 relative to optical media 102) and the opposite peakbeing at the acquisition starting position control effort. The startingfocus control effort can be applied to focus actuator 206 in step 705 byadding the starting focus control effort into the focus control effortat summer 521. This method of positioning elements, in both the focusand the tracking directions, can be widely utilized. In other words,whenever OPU 103 needs to be positioned relative to optical media 102, asmooth control effort as described above can be generated and applied.The resulting smooth motion of OPU 103 can reduce excitations ofmechanical resonances which may be obtained by application of moreabrupt control efforts.

[0218] If, in step 703, OPU 103 is already at an appropriate startingacquisition position, then algorithm 535 proceeds to step 706.Additionally, after the starting control effort is applied to focusactuator 206, then algorithm 535 proceeds to step 706.

[0219] In step 706, algorithm 535 generates an acquisition controleffort that moves OPU 103 from the starting acquisition position throughthe best focus position. Algorithm 535, in some embodiments, can providethe focus acquisition control effort required to move OPU 103 from thestarting acquisition position through the best focus position. However,again if mechanical resonances are excited in actuator arm 104, it maytake some time for the transient oscillations to damp out. Therefore, insome embodiments, step 706 calculates a sinusoidal focus acquisitioncontrol effort between the starting acquisition position and the controleffort corresponding to a position close to optical media 102. In someembodiments, the position close to optical media 102 may be the closestposition that OPU 103 can be moved toward optical media 102. Such afocus acquisition control effort profile is shown in FIG. 7C.

[0220] Once the focus acquisition control effort profile is calculated,then in step 707 DSP 416 is enabled to monitor the sum signal fromsummer 534, which generates the sum of all of the detector signals A, B,C, D, E, and F, and the FES signal output signal from summer 513 inorder to determine when focus has been acquired. In step 708, the focusacquisition control effort according to the focus acquisition controleffort profile calculated in step 706 is applied through summer 521 tothe focus control effort, and therefore applied to focus actuator 206 inorder to physically move OPU 103 through the best focus position.

[0221] In step 710, algorithm 535 monitors the closure criteria duringthe application of the focus acquisition control effort profile. If theclosure criteria is not satisfied, then algorithm 535 proceeds to step711. In step 711, algorithm 535 checks to see if the closest positionhas been reached. If in step 711, it is determined that OPU 103 has notyet reached the closest position, then algorithm 535 proceeds to step708 to continue to apply the focus acquisition control effort profile asthe focus control effort.

[0222] Step 710 can determine whether OPU 103 is close to the focusposition, in some embodiments, by the sum signal output from summer 534.In that case, if the sum signal is above a focus sum thresholddetermined by FES gain calibration 510, then OPU 103 is near to thefocus position. Furthermore, close to the focus position the FES signalwill be near zero. Therefore, in some embodiments the closure criteriaof step 710 can be that the sum signal is above a sum threshold and theFES signal is below an FES threshold.

[0223] If in step 710 algorithm 535 determines that the closure criteriais satisfied, algorithm 535 proceeds to step 712. In step 712, algorithm535 closes the focus loop without integrator 516 being enabled.Algorithm 535 then sets the current focus control effort to the biascontrol effort. In that case, step 712 maintains the focus controleffort from the acquisition focus control effort profile when the closedcriteria was satisfied. The acquisition focus control effort is heldconstant by algorithm 535 when focus is closed as long as focus remainsclosed.

[0224] In step 714, algorithm 535 delays for transient effects to decaybefore turning integrator 516 on in step 716. Algorithm 535 can furtherdelay in step 718 for transient effects to decay before enabling FESsample integrity test 515 in step 720. Once focus is closed andintegrator 516 and sample integrity test 515 are enabled, a focusacquisition complete flag can be set in step 723. In some embodiments,the “begin acquisition position” of step 704 may be recalibrated andstored for future executions of algorithm 535 in step 723.

[0225] If the closure condition of step 710 is not met, algorithm 535proceeds to closest position check step 711. If algorithm 535 determinesin step 711 that OPU 103 is at a closest position to optical media 102,then algorithm 535 sets a focus error bit in step 713. In someembodiments, the closest position can be the physically closest distancethat OPU 103 can be from optical media 102. In some other embodiments,however, the closest position refers to a closest allowable positionthat can be a predetermined value.

[0226] Once the focus error bit is set in step 713, algorithm 535 canproceed to step 715. In step 715, algorithm 535 determines a sinusoidaltracking control effort profile that moves OPU 103 away from opticalmedia 102 to a focus off position. As before, the sinusoidal trackingcontrol effort can be determined, as is shown in FIG. 7D, by fitting ahalf sine wave between the closest position and the focus off position.A focus control effort according to the sinusoidal tracking controleffort is applied to focus actuator 206 in step 717. Once OPU 103 hasreached the focus off position in step 719, then algorithm 535 exits ina failed condition in step 721. If focus acquisition fails, then errorrecovery routines can be initiated as is described in the SystemArchitecture disclosures. In some embodiments, the error recoveryroutines can attempt to execute focus close algorithm 535 multiple timesor change the “Begin Acquisition Position” in step 704 of algorithm 535shown in FIG. 7A.

[0227]FIGS. 8A and 8B illustrate an embodiment of multi-track seekalgorithm 557. FIG. 8A shows a block diagram of an embodiment ofmulti-track seek algorithm 557 while FIG. 8B shows signals as a functionof time for performing a multi-track seek function according to thepresent invention.

[0228]FIG. 8B shows the TES, tracking control effort, FES, and focuscontrol effort signals during a multi-track seek operation performed byalgorithm 557. During time period 821, focus servo algorithm 501 andtracking servo algorithm 502 are both on and tracking. At the beginningseek period 822, algorithm 557 generates a seek tracking control effortprofile which includes an acceleration tracking control effort 825 and adeceleration tracking control effort 827. A coasting or clamped trackingcontrol effort 826 can also be included between acceleration effort 825and deceleration effort 827.

[0229] The TES signal, then, begins to sinusoidally vary whenacceleration tracking control effort 825 is applied to tracking actuator360. The period of the sinusoidal variation indicates the track crossingvelocity. During acceleration, the period is decreasing indicating anincreasing track crossing velocity. In some embodiments, seek algorithm557 may clamp velocity at a particular value. Further, accelerationcontrol effort 825 and deceleration control effort 827 may be calculatedby controlling the actual acceleration of OPU 103 relative to opticalmedia 102 as measured with the varying period of the sinusoidal TES. InFIG. 8B, a track crossing velocity curve that may be generated by seekalgorithm 557 is shown, which indicates a constant acceleration theperiod when acceleration tracking control effort 825 is applied and aconstant deceleration the period when deceleration tracking controleffort 827 is applied. During period 823, seek algorithm 557 reacquiresa tracking on condition in tracking servo algorithm 502.

[0230] In some embodiments, during the seek operation the FES controleffort is selected in multiplexer 531 to be the low-pass filtered focuscontrol effort output by low pass filter 529 in order that TES-FEScrosstalk effects are minimized. In some embodiments, the output signalfrom sample and hold 530 is selected by multiplexer 531 during seekoperations. In some embodiments, seek cross-talk notch filter 590 canalso be enabled during the seek operation in order to reduce the effectsof the sinusoidal TES on FES. Therefore, in operation seek algorithm 557in some embodiments adjusts multiplexer 531 to receive the focus controleffort from filter 529 and can enable notch filter 590. Algorithm 557also adjusts multiplexer 558 to receive a tracking control effortgenerated by algorithm 557, turning tracking servo algorithm 502 off.Algorithm 557 then generates and applies a seek tracking control effortprofile, which is responsive to the velocity of OPU 103, and moves OPU103 to a target track on optical media 102. The velocity of OPU 103 canbe determined by measuring the period of the sinusoidally varying TES.Once algorithm 557 completes the actual move of OPU 103, then trackingis reacquired in close tracking algorithm 555 and multiplexer 558 isreset to receive the focus control effort signal from notch filter 553through switch 556. Further, multiplexer 531 is reset to pass the signaloutput from loop gain 524 as the focus control effort.

[0231]FIG. 8A shows a block diagram of an embodiment of algorithm 557.The TES' signal output from TES sample integrity test 548 is received byTrack Zero Crossing (TZC) detector 801. TZC detector 801 determines thetrack crossings and, in some embodiments, each time a track is crossedgenerates a pulse signal. In some embodiments of the invention,algorithm 557 may read the TZC signal from track crossing detector 454(see FIG. 4). In some embodiments, TZC detector 801 receives a defectsignal from defect detector 591. The defect signal disables the TZCdetector output from generating a pulse during the presence of a mediadefect. The TZC signal is input to TZC counter 802 and TZC period 803.TZC detector 554 of FIG. 5B includes TZC detector 801 and TZC period803. TZC counter 802 counts the number of tracks crossed. The Directionsignal from Direction Detection 592 determines the direction TZC counter802 counts. For example, if a direction reversal occurs near the end ofa seek possibly due to an external disturbance, then the counter willincrement instead of decrement. This assures the seek crosses thecorrect number of tracks. TZC period 803 calculates the time periodbetween successive track crossings. Seek completion detection 816monitors the number of tracks crossed from TZC counter 802 and indicateswhether seek is complete. Seek complete detection 816, therefore, alsoindicates the number of tracks remaining to the target track. Inaddition, seek complete detection 816 can output a retro-rocket signalwhich can enable retro-rocket gain 830. In some embodiments, seekcompletion 816 indicates that the seek is completed when the countexceeds the target count and when the TES signal has an appropriateslope in which to close tracking.

[0232] In some embodiments, TZC counter 802 receives a signal indicatingeach full rotation of optical media 102. During seek operations, opticalmedia 102 continues to rotate. The rotations can cause additive seeklength error to the actual seek length if the seek servo simply countstrack crossings in TZC counter 802 instead of taking the track spiralinto account. Predicting the number of disk rotations based upon seeklength could be used; however, this method does not account for seektime variations caused by outside factors such as, for example,mechanical disturbances. TZC counter 802, by incrementing the TZC countduring seeks on each rotation of optical media 102, can prevent errorsin seek length.

[0233] A velocity profile is calculated in reference velocitycalculation 805. The velocity profile calculated in reference velocitycalculation 805 can, as shown in FIG. 8B, be optimized to move OPU 103to the target track in a minimum amount of time without excitingresonances and stop OPU 103 at or very near the target track. FBvelocity calculation 806 receives the measured track crossing periodfrom TZC period 803 and calculates the actual velocity of OPU 103. Thedifference between the reference velocity calculation from calculation805 and the actual velocity as calculated by calculation 806 is formedin summer 807, which outputs a velocity error value. In someembodiments, the output signal from calculation 806 is input to a signblock 818 which, based on the direction signal from direction detector592, multiplies the calculated FbVEL value from block 806 by the sign ofthe direction signal.

[0234] In some embodiments, FB Vel calculation 806 calculates thevelocity based on the time between half-track crossings. In someembodiments, at higher velocities, two consecutive half-track periodscan be averaged. The sampling rate of algorithm 557 is the half-trackcrossing rate, which can be quite low (e.g. 2 kHz at track capture)resulting in a low bandwidth closed loop seek servo. The low bandwidthleaves the seek servo vulnerable to shock and vibration disturbancesduring the critical track capture phase of the seek operation. It isdesirable to achieve good velocity regulation particularly whenapproaching the track capture phase of the seek. This bandwidth can beimproved, and thus the velocity regulation upon track capture can beimproved, by calculating the derivative of the TES when the TES iswithin a reasonable linear range of it's sinusoidal curve while crossingtracks. The derivative measurement is averaged with the most recent halftrack crossing measurement to filter some of the inherent noise effectsassociated with differentiation. Additionally, the positive and negativeslopes of the TES are not symmetric, therefore, a balance gain isapplied to one of the TES slopes to eliminate the effect of thisasymmetry on the derivative calculation. In these embodiments, then, theFbVEL parameter is given by FbVEL=[(K1/TzcPeriod)+K2*d(TES)/dt]/2, whereK2=K2a for track enter slopes and K2=K2b for half track center slopes.Typically, K2a=−0.7K2b.

[0235] The velocity error from summer 807 is multiplied by a constant K₃in step 809 and input to summer 813. Further, velocity error is summedwith the sum of velocity errors measured during previous clock cycles insummer 810, multiplied by constant K₄ in step 812, and added to theoutput value from step 809 in summer 813. Summer 810 acts as anintegrator, integrating the velocity error. The output value from summer813 is input to multiplexer 814. The output signal from multiplexer 814is input to loop gain 815, which generates a tracking control effort.The tracking control effort output by loop gain 815 is part of the seektracking control effort profile which moves OPU 103 to the target trackin a controlled fashion.

[0236] In some embodiments, the tracking control effort output frommultiplexer 814 can be a clamped acceleration effort generated byacceleration clamp 808. Acceleration clamp 808 monitors the accelerationof OPU 103 from the velocity error determined in summer 807 and, if amaximum acceleration value is exceeded, limits the tracking controleffort to be the maximum acceleration value.

[0237] In some embodiments, the TES' signal is also input to boundarydetector 817. In general, multi-track seeks can cross boundaries betweenwriteable 151 and pre-mastered 150 portions of optical media 102 (FIG.1B). The operation of direction sensor 592 as well as many operatingparameters, including the TES gain, TES offset, FES gain, FES offset,and cross-talk compensation parameters from cross-talk calibration 579will be different depending on whether OPU 103 is over a writeable orpre-mastered portion of optical media 102. Boundary detector 817includes a multi-point positive and negative TES peak averagingalgorithm, which is executing during seek operations. Boundary detector817 then monitors the TES peak-to-peak amplitude during seeks. Beforeinitiating a seek operation, algorithm 557 knows the type of media (i.e.pre-mastered, grooves, or write able, bumps) that OPU 103 is over.Microprocessor 432 can inform algorithm 557, which is usually operatingon DSP 416, whether or not the seek operation takes OPU 103 from onetype of media to another. If a boundary crossing is detected, thenboundary detector 817 can monitor to determine when the boundary hasbeen crossed.

[0238] Boundary detector 817 detects the boundary crossing byidentifying when the TES peak-to-peak amplitude (TESPP), for examplecalculated by the multi-point peak averaging, by more than a thresholdvalue (for example 25% of TESPP).

TesPP Change=|TesPP(k)−TesPP(k−2|where k represents the measurementnumber

[0239] If the threshold value is set too high, the boundary crossingalgorithm may miss boundary crossings. Alternatively, if the thresholdvalue is set too low, the boundary crossing algorithm may erroneouslydetect boundary crossings. In some embodiments, a default threshold canbe utilized for a first boundary crossing on a newly inserted disk. Whenthe boundary is detected, the measured change in TES peak-to-peak valuecan be averaged with the default threshold to drive the thresholdamplitude in the direction of the actual change in TES peak-to-peak forthe specific one of media 102. The averaging process can continue forall subsequent boundary crossings while the specific one of media 102 isin drive 100. The threshold, then, can be set to the averaged thresholdfor all future boundary crossings in that specific media 102.

[0240] In some embodiments, consecutive TesPP measurements are notcompared because one of these measurements may straddle a boundarybetween media when making the multipoint peak averaging measurement. Atthat point, boundary detector 817 determines that the boundary has beencrossed and switches the media sensitive operating parameters toparameters appropriate for the new media.

[0241]FIGS. 9A and 9B shows a flow chart of an embodiment of seekalgorithm 557. In seek initialization 901, seek command 902 is issued,for example by microprocessor 432. Further, an acceleration flag, a seekdirection flag, a TZC period, and a seeklength (indicating target track)are set in initialization 903. In some embodiments, laser power may bereduced during a seek operation. Therefore, in seek initialization 901,laser power can be reduced as well. Upon completion of the seekoperation, laser power can be reset to a read power level.

[0242] In step 904, a TZC period count variable is incremented. In step905, the TZC period count variable is checked against the current TZCperiod variable and, if at least half or some other fraction of the mostrecently measured TZC period has not elapsed, algorithm 557 proceeds toskip TZC period and counter calculations 803 and 802. If the conditionof step 905 is met, then algorithm 557 proceeds to crossing detection906. Crossing detection 906 indicates a crossing TZC if the TES' valuecrosses 0. Crossing detection 906 includes amplitude hysterisis inaddition to the temporal hysterisis provided in step 905, i.e., that thenext TZC crossing can not be indicated again for at least half the oldTZC period value, which prevents noise from falsely indicating a TZCcrossing.

[0243]FIG. 9C illustrates the TZC detection algorithm performed by TZCdetector 801. TZC detector 801 provides a change in state on each zerocrossing. As shown, however, TZC detection 906 of TZC detector 801provides a change of state on each detected zero crossing. TZC detection906, from step 905, is enabled to change after about ½the TZC period.Additionally, in step 906, the TZC crossing provides a low thresholdvalue and a high threshold value so that, on an increasing TES' signal,the TZC zero is detected at the high threshold value and on a decreasingTES' signal detects the TZC zero at the low threshold. A amplitudehysterisis is then provided.

[0244] In step 907, algorithm 557 indicates whether the TZC value haschanged, indicating a track crossing. If not, then calculation of TZCperiod and updating of track counting in steps 803 and 802 are skipped.If the TZC value has changed, then algorithm 557 proceeds to block 908.In block 908, if the acceleration flag is not set or if the currentcount for TZC period (the TZC period count variable) is less than somemultiple (for example twice) of the most recently measured TZC period orif the TZCSkip flag is set, then algorithm 557 proceeds to step 909,else algorithm 557 proceeds to step 910 which sets the TZC skip flag.From step 910, algorithm 557 then proceeds to step 913, which resets theTZC period count to zero. If the conditions of step 908 are met, thenalgorithm 557 proceeds to step 909.

[0245] Step 909 checks whether the currently detected TZC pulse is thefirst pulse and, if so, proceeds to step 913 where the TZC period countvariable is set to 0. Otherwise, algorithm 557 proceeds to step 911which sets the TZC period to the current TZC period count. Algorithm 557then clears the TZCskip flag in step 912 before resetting the TZC periodcount in step 913.

[0246] Steps 908 through 912, perform a TZC period integrity test. Insome embodiments, the TZC period is checked against the previouslymeasured TZC period (i.e., the TZC period of cycle k is compared withthe TZC period of cycle k−1). An error is generated if the TZC period ofcycle k varies substantially from the TZC period of cycle k−1. In someembodiments, since a new zero crossing is not detected until at least ½the TZC period of cycle k−1 (see step 905), and step 908 checks to besure that the TZC period in the kth cycle is less than twice the TZCperiod in the k−1th cycle, then the TZC period is restrained to bebetween ½ TZC period and 2 the TZC period of the k−1th cycle (i.e.,TZCperiod(k−1)/2<TZCperiod(k)<2*TZCperiod (k−1). In some embodiments,the range can be extended. For example, in some embodiments TZCperiod(k−1)/4<TZCperiod (k)<4*TZCperiod(k−1).

[0247] In step 914, the direction is checked, for example by checkingthe direction signal from direction detector 592 (FIG. 5A), so that theTZC count variable can either be decremented in block 915 or incrementedin block 916, depending on direction. Algorithm 557 then proceeds tostep 917.

[0248] In step 917, algorithm 557 checks if the current calculatedreference velocity, which is a constant times the TZC count parametercalculated in block 802 of FIG. 8A, is greater than a maximum value ofthe reference velocity. If the reference velocity is greater than halfthe value of the maximum, then the TZC period value is averaged withprevious TZC period values in step 918, which can have the effect ofsmoothing the actual velocity measurement. Algorithm 557 then proceedsto step 919 of seek completion detection 816.

[0249] Step 919 checks the current value of the TZC count to see if therequired number of tracks have been crossed. If not, then algorithm 557proceeds to step 922 of algorithm 805. If the number of track crossingsis correct, then algorithm 557 checks in step 920 to see if the TES' hasthe correct slope. If not, the algorithm 557 proceeds to step 922. Ifthe slope is correct, then algorithm 557 sets a seek completion flag instep 921 and exits. Tracking can then be reacquired in tracking closealgorithm 555.

[0250] In step 922, a reference velocity is calculated. The referencevelocity is greater than a minimum reference velocity by a valueproportional to the track crossing count TZC count. The sign of thereference velocity is the sign of the TZC Count. For example, a 100track seek toward the inner diameter (ID) would initialize the TZC countwith +200 (since TZC counter counts half tracks) and the counter woulddecrement (assuming the direction sensor determines that OPU 103 ismoving toward the ID) for each half track crossing until reaching thedestination track with a count of 0. Thus, the reference velocity wouldbe positive for seeks toward the ID. A 100 track seek toward the ODwould cause the TZC counter to be initialized with a negative 200 value.The counter would increment (assuming the direction sensor determinesthat OPU 103 is moving toward the OD) until reaching 0 at thedestination track. The reference velocity has a negative sign for seekstoward the OD.

[0251] In step 923, the reference velocity calculated in step 922 iscompared with a maximum reference velocity and, if the maximum referencevelocity is exceeded, then the reference velocity is reset to themaximum reference velocity in step 924. In step 806, the actual velocityof OPU 103 is calculated. The actual velocity (FbVEL) is proportional tothe reciprocal of the TZC period variable, which is calculated in block803 of FIG. 8A. Step 807, then, calculates the velocity error as thedifference between the reference velocity and the actual velocity.Algorithm 557 then proceeds to step 934.

[0252] In step 934, algorithm 557 checks for the first change in sign ofthe velocity error signal. If the sign of the velocity error has not yetchanged since the start of seek, then the seek acceleration phasecontinues. If the first change in the velocity error sign is detected,then the acceleration flag is cleared in step 935. During the initialphase of the seek (a.k.a. acceleration phase), the velocity of OPU 103must be accelerated until it's velocity reaches the reference velocity.Until then, the velocity error can be large. It is desirable to notallow multi-track seek control compensator's integrator, which includessummer 813, from operating during the initial phase of seek because itwill integrate this large velocity error resulting in a significantfeedback velocity overshoot of the reference velocity. In addition, thecontrol effort during this acceleration phase of a multi-track seekoperation is clamped by clamp 808 to avoid accelerating too fast whichcould also cause significant overshoot of the reference velocity.Otherwise, algorithm 557 sets the seek control effort proportionally tothe seek control variable in step 815. Algorithm 557 then proceeds tostep 804 where tracking phase lead 550 can be updated to properlyinitialize it's states in order to reduce the time required to reacquiretracking in close tracking algorithm 555. From step 935, algorithm 557proceeds to step 927.

[0253] In step 927, if OPU 103 is accelerating, then a seek controlvariable is set to the velocity error in step 928. In step 929, the seekcontrol variable is compared with a maximum acceleration variable and,if the maximum acceleration variable is exceeded, then seek control isset to maximum acceleration in step 930. If not exceeded, then algorithm930 proceeds to step 934.

[0254] If step 927 determines that there is no acceleration, thenalgorithm 557 proceeds to step 931. If the velocity error is greaterthan a maximum velocity error, and there has not been too manysuccessive corrections, then algorithm 557 proceeds to step 933, whichsets the seek control variable to be a constant times the velocity errorplus a value proportional to an integral of the velocity error, as shownin FIG. 8A as steps 809,813, 810, 811, and 812. If the maximum velocityerror is not exceeded in step 931, then velocity error is set to 0 instep 932 and seek control is set to a value proportional to the velocityerror integral in step 933. Algorithm 557 then proceeds to step 815.

[0255] In some embodiments, completing a seek operation in algorithm 557also begins a time limited tracking loop high gain mode, which can bereferred to as a “retro rocket.” Seek completion detector 816 can enableretro-rocket gain 830 The tracking servo phase lead compensator 550(FIG. 5A) states know about the tracking and velocity error at theinstant of the seek to tracking transition as a result of properlyinitializing the phase lead compensator. Therefore, tracking servo 502knows whether to accelerate or decelerate for capturing the destinationtrack center. By significantly increasing the tracking loop gain(bandwidth) for a predetermined number of servo samples (for example 5),tracking servo 502 can more aggressively acquire the destination track.Time constraining the duration of the increased tracking loop gain canprevent the instabilities caused by mechanical resonances from growingunbounded and thus destabilizing the system. The net effect of applyingthe retro-rockets is a very aggressive closed loop track captureconverged upon track center quickly followed by a nominal bandwidth verystable tracking control system closed on the destination track.

[0256] In some embodiments, algorithm 557 is executed as part of acontrol loop on DSP 416. In those embodiments, seek algorithms may beexecuted, for example, every 20 μs (i.e., 50 kHz). However, as morefilly discussed below, detector signals A, B, C, D, E, and F areavailable every 10 μs, or at 100 kHz. In some embodiments, algorithm 557may be solely operated on DSP 416 so that the full 100 kHz availabilityof data is available.

[0257]FIG. 10B shows a block diagram of a one-track jump algorithm 559.FIG. 10A illustrates the TES, tracking control effort, FES, and focuscontrol effort during a one-track jump algorithm. The TES and FESsignals shown are the output signals from summer 506. The TES and FESsignals shown in FIG. 10B are measured scope traces from output pwm's474, who's output signals are centered about reference voltages, e.g.from block 462 (FIG. 4). As shown in FIG. 10A, a one-track jumpalgorithm starts in a tracking mode 1001 and includes an accelerationperiod 1002, a coast period 1003, and a deceleration period 1004. Oncedeceleration period 1004 is complete, a settling period 1008 is followedby a focus on 1005 and a tracking integrator on 1006. At which time, atracking and focus period 1007 is initiated.

[0258] In FIG. 10A, during tracking period 1001 both focus servoalgorithm 501 and tracking servo algorithm 502 are on, therefore drive100 is tracking and focusing on a starting track. During accelerationperiod 1002, one-track jump algorithm 559 applies an accelerationtracking control effort to tracking DAC 468 which accelerates OPU 103 inthe desired tracking direction for a fixed time. During coast period1003, one-track jump algorithm 559 holds the tracking control effort atthe level applied before the one track jump algorithm begins. In someembodiments, coast period 1003 is held until the TES signal output fromsample integrity test 548 changes sign, indicating a half-trackcrossing. Finally, during deceleration period 1004 one-track jumpalgorithm 557 applies a deceleration tracking control effort to trackingDAC 468. As shown, the acceleration tracking control effort ofacceleration period 1002 and the coast period 1003, and the decelerationtracking control effort of deceleration period 1004 causes TES to passthough one period of the TES versus position curve, indicating a singletrack crossing. At some time 1006 after deceleration period 1004 ends,one-track jump algorithm 559 re-enables low frequency integrator 549,which was disabled but not reset when algorithm 559 began. Further,during acceleration period 1002, coast period 1003, deceleration period1004 and until time 1005 after deceleration period 1004, sample and hold530 holds the focus control effort at a constant level. When one-trackjump algorithm 559 completes, servo control algorithm 500 re-enters amode of tracking both focus and track position.

[0259] In some embodiments, the time scale on FIG. 10A is of the orderof hundreds of microseconds so that, for example, the numbered divisionsare on the order of 200 microseconds. In some cases, one-track jumpalgorithm 559 can be executed in DSP 416 since microprocessor 432 may beunable to respond fast enough.

[0260]FIG. 10B shows schematically a block diagram of one-track jumpalgorithm 559. Tracking compensation 1011 includes integrator 549, phaselead 550, and notch filters 551 through 553. Therefore, the outputsignal from tracking compensation 1011 is the tracking control effortgenerated through the closed tracking servo system 502 that is input tomultiplexer 558. Multiplexer 558 in FIG. 10B is represented by a switch.Track jump state machine 1010, when one track algorithm 559 isinitiated, controls multiplexer 558 so that the tracking control effortgenerated by algorithm 559 is ultimately applied to tracking actuator201 instead of the tracking control effort signal generated by trackingcompensation 1011. In FIG. 10B, the tracking control effort output fromtracking DAC 468 is input to summer 1020 which is located in powerdriver 340. As was discussed above, the tracking control effort outputfrom DAC 468 is summed with the bias control effort by summer 1020 inpower driver 340. Plant 1021 includes tracking actuator 201 as well asOPU 103 and actuator arm 104.

[0261] The tracking control effort from tracking compensation 1011 islow pass filtered in filter 1012 and input to sample and hold 1017.During execution of one-track jump algorithm 559, the output signal fromsample and hold 1017 is fixed at a constant value. The constant trackingcontrol effort output from sample and hold 1017 is summed with theone-track jump tracking control profile generated in algorithm 559 atsummer 1016.

[0262] The one-track jump tracking control profile includes anacceleration pulse generated by pulse amplifier 1013 and a decelerationpulse generated by pulse amplifier 1014. Track jump state machine 1010controls the amplitude and duration of acceleration and decelerationpulses. Track jump state machine 1010 further controls the direction ofthe one-track jump by determining the sign of the amplitudes of theacceleration and deceleration pulses generated by pulse amplifiers 1013and 1014.

[0263] In some embodiments, the amplitude and duration of accelerationand deceleration pulses are set during a calibration step in calibrationalgorithm 560. In some embodiments, the amplitude and duration ofacceleration and deceleration pulses may change as a function ofposition of OPU 103 over optical media 102. Further, although in FIG.10B, the jump control effort profile is shown as including a positiveand negative square wave pulse, in some embodiments acceleration pulseand deceleration pulse may include sinusoidal wave pulses in order toavoid exciting mechanical resonances in actuator arm 104.

[0264] Track jump state machine 1010, then, first latches sample andhold 1017, shuts off low frequency integrator 549, and latches sampleand hold 530, then applies the acceleration pulse from pulse amplifier1013. State machine 101 then monitors the TES' signal for a sign change.When the sign change is detected, state machine 1010 applies thedeceleration pulse generated by pulse amplifier 1014. If a sign changeis not detected within a set period of time, then track jump statemachine 1010 indicates a failed jump condition. In those circumstances,error recovery routines (See System Architecture disclosures) willrecover from this condition.

[0265] Once the deceleration pulse has ended, state machine 1010switches multiplexer 558 to receive tracking control efforts fromtracking compensation 1011, and delays for a period of time to allowtransient effects to decay. State machine 1010 then turns focus back on(by setting multiplexer 531 to accept the focus control effort ratherthan the output signal from sample and hold 530) and re-enablesintegrator 549.

[0266] In some embodiments, one-track jump algorithm 559 shown in FIG.10B, for example, can further include notch filters 551 and 553 forreceiving the one-track jump control effort profile output from summer1016. Further, as is shown and discussed further below, algorithm 559can be executed on DSP 416 in a timer interrupt mode. In someembodiments, one track algorithm 559 initiates phase lead 550 so thatphase lead 550 is initiated to the proper state when tracking is closedfollowing the one-track jump operation. Initializing phase lead 550improves dynamic response during the close tracking operation. Further,during a one-track jump algorithm, the focus control signal can be setto the output of sample and hold 530, which holds the output signal fromlow-pass filter 529 during the one-track jump operation.

[0267]FIG. 11 shows a block diagram of a DSP firmware architecture 1100according to the present invention. As discussed above, microprocessor432 and DSP 416 can communicate through mailboxes 434. Initializationblock 1101, main loop block 1102, timer interrupt block 1103, and sensorinterrupt block 1120 represent algorithms executing on DSP 416. Ininitialization 1101, all of the filter states in FIGS. 5A and 5B are setto zero and all initializations are accomplished. Main loop 1102represents an infinite loop that actually does nothing, since in mostembodiments DSP 416 is interrupt driven. Timer interrupt 1103 executesone-track jump algorithm 559.

[0268] Focus and tracking servo algorithms are executed as part ofsensor interrupt 1120. Sensor interrupt 1120 is available when all ofthe detector sensor signals A, B, C, D, E and F are available atdecimation filters 414-1 and 414-6 (FIG. 4). Therefore, in someembodiments (for example), there is a sensor interrupt at a frequency of100 kHz frequency, which occurs every 10 μs. Therefore, every 10 μs DSP416 receives a sensor interrupt which initiates sensor interrupt code1120 shown in FIG. 11.

[0269] In step 1104, algorithm 1120 determines which algorithm toexecute, focus or tracking. Focus servo algorithm 501 and tracking servoalgorithm 502 alternate, therefore each is executed every 20 μs.Therefore, focus and tracking loops are sampled at 20 μs or 50 kHzrather than interrupting every 20 μs and executing both focus andtracking algorithms. In this fashion, there is a lower time delaybetween sampling detector signals A, B, C, D, E, and F. In someembodiments, a third loop in algorithm 1120 can execute a spin-motorservo algorithm (see the Spin Motor Servo System disclosures). However,DSP 416 operates very fast but has limited resources in terms of memory.

[0270] If algorithm 1120 executes focus servo algorithm 501, then anFES' signal is calculated in step 1111. The FES' signal is the outputsignal from sample integrity test 515, therefore step 1111 includesfocus servo algorithm 501 through integrity test 515. In someembodiments, defect detection algorithm 591 can then be calculated,providing a defect signal to a write abort algorithm which may beoperating on microprocessor 432.

[0271] When the FES' signal is calculated in step 1111, algorithm 1120proceeds to step 1112. In step 1112, algorithm 1120 determines if focusis on. In some embodiments, algorithm 1120 determines that focus is onor off by checking a bit flag in a control word held in mailboxes 434.If focus is off, then algorithm 1120 is finished with the focusoperation and proceeds to step 1114. If focus is on, the algorithm 1120finishes the operations of focus servo algorithm 501 in step 1113. Afterstep 1113, then algorithm 1120 proceeds to step 1114.

[0272] If tracking servo algorithm 502 is chosen in step 1104, thenalgorithm 1120 proceeds to step 1105. In step 1105, tracking servoalgorithm 502 through TES sample integrity test 548 is executed tocalculate a TES' value. Algorithm 1120 then proceeds to step 1106. Instep 1106, algorithm 1120 determines if a seek operation is beingundertaken, in some embodiments by checking a seek flag set in a controlword held in mailboxes 434.

[0273] If a seek operation is being undertaken, then algorithm 1120proceeds to seek algorithm 557 in step 1107. Step 1107 can perform manyof the steps described with FIGS. 8A, 8B, 9A and 9B describing seekalgorithm 557. Additionally, some of the steps shown in FIGS. 9A and 9Bcan be performed through tasks in multiplexer 1116, as described below.For example, seek initialization 901 can be performed as tasks inmultiplexer 1116.

[0274] If there is no current seek operation, or when step 1107 iscompleted, algorithm 1120 proceeds to step 1108. In step 1108 algorithm1120 determines whether tracking is on or not. If tracking is on, thenalgorithm 1120 proceeds to step 1109 where the remaining portion oftrack servo algorithm 502 is executed. If tracking is off, or when step1109 is completed, algorithm 1120 proceeds to step 1110. Usually,algorithm 1120 either executes step 1107, step 1109, or neither.However, in some cases a seek operation may finish in step 1107 and thentracking should be turned on in step 1109, in which case both steps 1107and 1109 are executed during the same interrupt.

[0275] In step 1110, minimum and maximum calculations on any variablecan be calculated. The particular variable can be chosen bymicroprocessor through mailboxes 434. Step 1110 allows variables to bemonitored and trace data to be kept for calibration routines ormonitoring routines. From step 1110, algorithm 1120 proceeds to step1114.

[0276] In step 1114, algorithm 1120 determines if the drive is in thecoast mode of a one-track jump. If step 1114 indicates a coast mode of aone-track jump, which in some embodiments can be determined by checkingthe appropriate bit flag in a control register of mailboxes 434, thenalgorithm 1120 proceeds to step 1115. Step 1115 determines if thedeceleration step of the one-track jump should be started and, if so,starts the deceleration step. Once step 1115 is complete, or if step1114 determines that there is no one-track jump operation, thenalgorithm 1120 proceeds to multiplexer 116.

[0277] One track jump algorithm 559, as discussed with FIGS. 10A and10B, execute in a timer interrupt mode. However, algorithm 1120 operatesevery 10 microseconds, which allows steps 1114 and 1115 to execute every10 microseconds, in embodiments operating at a frequency of 100 kHz. Thetimer interrupt from one track jump algorithm 559 has a lower interruptpriority than sensor interrupts that trigger algorithm 1120. Sensorinterrupt allows step 1114 to start deceleration in step 1115.

[0278] Multiplexer 1116 includes tasks that can be done after either thetracking loop or the focus loop processing is completed if any of theexecution time is available before the next sensor interrupt. Typically,the tasks included in multiplexer 1116 can be tasks that do not need tobe serviced as frequently as do focus and tracking algorithms. Forexample, one task that can fall into multiplexer 1116 is TES OK 517. Asdiscussed before, TES OK 517 checks the FES signal and, if the FESsignal is too high, determines that the TES signal is unreliable.However, tracking servo algorithm 502 does not need to be immediatelyshut down, so the TES OK task can wait until its turn in multiplexer1116. In some embodiments, multiplexer 1116 can include 16 tasks.Another example of a task that can be included in multiplexer 116include reading new variables from mailboxes 434 and updating variablesused in other areas of algorithm 1120. In that fashion, ifmicroprocessor 432 adjusts a gain or offset value utilized in focusservo algorithm 501 or tracking servo algorithm 502, then a task inmultiplexer 1116 can read that gain or offset and update the appropriatevariables. Some tasks that may be executed in multiplexer 1116 includefocus loop OK algorithm 536, turn focus off algorithm (when commanded todo so), clear focus bad flag, zero the states of low frequencyintegrator 549, move the TES and FES gain and offset variables frommailboxes to internal variables, zero the low pass filter states ofskate detector 561 if skate detector 561 is disabled, close trackingalgorithm 555, initialize one-track jump algorithm 559, reset the jumpstatus, initialize the seek variables of multi-track seek algorithm 557and begin the seek, reset the seek status, clear write-abort status ofwrite abort algorithm 537, seek length spiral compensation in algorithm557, calibrate notch filter coefficients of notch calibration algorithms520 and 552, provide general purpose mailbox communications.

[0279] From multiplexer 1116, algorithm 1120 proceeds to update statusmailbox 1117, which writes status bits to mailboxes 434 as required. Forexample, error interrupts to microprocessor 432 can be set at step 1117.Algorithm 1120 then proceeds to step 1118 where diagnostic data can bemaintained.

[0280] In some instances, algorithm 1120 may take more time to completeone cycle than there is time between sensor interrupts. In that case,some sensor interrupts may be missed. However, if too many interruptsare missed or if there is not enough idle time between interrupts, therecan be instabilities developed in some embodiments.

Example Embodiments of Calibration Algorithms

[0281] In some embodiments, dynamic calibrations can be performed oncomponents of drive 100 in order to dynamically optimize operation ofdrive 100. Several calibration algorithms have been mentioned in thepreceding discussion on signal processing, including the followingcalibrations: detector offset calibration 548 (FIG. 5A) and detectorgain calibration 583 (FIG. 5A), which calibrates the offset and gainparameters for offsets 402-1 through 402-6 (FIG. 4) and amplifiers 404-1through 404-6 (FIG. 4), respectively; FES offset calibration 508 forcalibrating the FES offset applied to summer 507 (FIG. 5); FES gaincalibration 510 for calibrating FES gain amplifier 509 (FIG. 5); inversenon-linearity calibration 512 which calibrates inverse non-linearityalgorithm 511 (FIG. 5); TES-to-FES cross-coupling gain calibration 579for calibrating TES-to-FES cross-coupling gain 514, which cancels atleast partially TES-to-FES cross coupling in the FES signal; notchcalibration 520 for calibration of notch filter 519; focus loop gaincalibration 522 for calibrating the loop gain of focus servo algorithm501; calibrated feed-forward gain 532; TES offset calibration 542 forsetting the TES offset applied in summer 541; TES Gain calibration 544which set the gain of gain 543; inverse nonlinearity calibration 547which calibrates inverse nonlinearity algorithm 546; notch calibration552 which calibrates notch filter 551; calibration algorithm 560 whichcalibrates one-track jump algorithm 559; loop gain calibration 562 forcalibrating TES servo algorithm 502; and calibrated feed-forwardalgorithm 579. In some embodiments of the invention, furthercalibrations can be added. For example, low frequency integrators 516and 549 may be calibrated.

[0282]FIG. 12A shows a block diagram of an example calibration life-timefor drive 100. As indicated by state 1201, many calibrations withindrive 100 are set, or at least initially set, when drive 100 isfabricated. These settings can, for example, include initial values forcontrolling power supplies or for calibrating motor servo parameters.FIG. 12B shows a chart of an example of several operating parameters andwhen those parameters can be calibrated and at what stage in calibrationthose parameters are calibrated. Initial default values for tracking andfocus servo system parameters can also be initialized during initialdrive calibration 1201. For example, offset and gain values fromdetector offset calibration 584 and detector gain calibration 583, notchfilter calibrations 520, and notch filter calibration 552 can be set atthis time. In operation, calibration algorithm 1201 can load defaultvalues for each of the calibration parameters and adjust them for theparticular characteristics of drive 100 operating with a standardizedoptical media 102.

[0283] Once the particular factory calibration parameters are determinedin initial calibration 1201, then in some embodiments factorycalibration values can be stored in program memory 330, which caninclude a flash memory. In some embodiments, media specific calibrationparameters, which can, for example, include detector input parameters todetector offsets 402-1 through 402-6 and gains 404-1 through 404-6, FESoffset from calibration 508, TES offset from calibration 542, FES gainfrom calibration 510, TES gain from calibration 544, focus loop gainparameters from loop gain 522, tracking loop gain parameters from TESloop gain 562, calibration parameters for inverse non-linearityfunctions algorithms 511 and 546 (FES inverse non-linearity parametersand TES inverse non-linearity parameters, respectively), notch filterparameters for notch filters 519 and 551, and one track jumpcalibrations 560, can be written onto optical media 102 so that, whendrive 100 “wakes up” with a particular optical media, the best operatingparameters for optical media 102 can be read and utilized. In someembodiments, the best average operating parameters can be stored inprogram memory 330 and drive 100 can start with those parameters. Theaverage parameters stored in program memory can be updated each timedrive 100 is calibrated.

[0284] Initial calibration 1201 can also be repeated during a rework orrepair calibration 1202. Calibration 1201, then, can be repeated whendrive 100 is, for some reason, returned for repair.

[0285] Calibration cycle 1203 represents normal, in-service,calibrations for drive 100. Calibration 1203 can be executed, forexample, whenever a new optical media 102 is loaded, when drive 100 isstarted, and during an error recovery algorithm (see the MicrocodeSystem Architecture disclosures). In some embodiments, when drive 100 isinitially started (i.e., “wakes up”), cycle 1203 receives default valuesfor calibration parameters from flash memory 330. In some embodiments,media specific calibration parameters can be read from optical media102. In some embodiments, default values for drive specific and mediaspecific parameters can be stored in program memory 330 (FIG. 3) andloaded when drive 100 is powered. In some embodiments, temporary mediaspecific parameters can be stored in memory 330 so that, when drive 100is re-started, the preceding parameters can be utilized. Since drive 100may often be started with the same optical media as when it was shutdown, stored parameters can save time in “waking-up” drive 100.

[0286] In some embodiments, default parameters may be changed over time.As drive 100 ages, many of the default parameters can become verydifferent from the initial calibration parameters required to operatedrive 100. Therefore, in some embodiments of drive 100, the actual driveparameters may be re-stored as default parameters. In some embodiments,an average of the actual drive parameters with the default parametersmay be re-stored as default parameters. However, if drive 100 isoperated in extreme environments or if optical media 102 is particularlyproblematic (e.g., if optical media 102 is severely not flat due toexposure to heat or other warping environments), then the actualparameters required to operate under those conditions should not replaceor alter the current default parameters. Therefore, in some embodimentsif the current parameters vary beyond threshold values from the defaultparameters, the default parameters are not replaced or altered by theseparameters.

[0287]FIG. 12B shows drive specific parameters which are calibrated. Ingeneral, as discussed above, optical media 102 can have a pre-masteredportion (which is read only) and a writable portion (which isread/write). In general, operating parameters are calibrated foroperation of drive 100 under all of these conditions, i.e. readoperation over the writable portion of optical disk 102, write operationover the writable portion of optical disk 102, and read operation overthe pre-mastered portion of optical disk 102.

[0288]FIG. 13A shows an embodiment of a calibration sequence 1350 forcalibrating over each media type of an optical media 102 and for readand write, where appropriate, modes over those media types. In general,optical media 102 can have several media types and several regions withdiffering media types.

[0289] Sequence 1350 starts with step 1351 where a first set ofconditions is set. For example, the first set of conditions can be aread mode over a pre-mastered portion of optical media 102. In step1352, preamplifier 310 (FIG. 3A) is set for the correct mode (e.g., reador write). In step 1353, laser power to laser servo 105 is set to theappropriate power for that mode. In step 1354, OPU 103 is positionedover the selected media type (e.g., pre-mastered or writable). In step1301, a calibration algorithm 1301 is executed. Calibration algorithm1301 executes a sequence of calibration routines that are appropriatefor the selected mode and selected media type and stores the operatingparameters for use in disk drive 100. In step 1355, sequence 1350 checksto determine if all combinations of operating modes and media types havebeen calibrated. If there are more combinations, then sequence 1350proceeds to step 1357 where the next combination of operating mode andmedia type is selected. From step 1357, sequence 1350 proceeds to step1352 to calibrate the next combination. When all combinations arecalibrated, algorithm 1350 finishes at step 1356.

[0290]FIG. 13B shows an embodiment of an example calibration routine1301 which can be executed either during initial drive state 1201 orrework state 1202. Calibration routine 1301 shown in FIG. 13B, forexample, would be appropriate for a read mode calibration ofpre-mastered media. In some embodiments, as illustrated in state 1203,calibration algorithm 1301 can be executed whenever drive 100 isstarted-up or whenever a new optical media 102 is inserted into drive100. When algorithm 1301 is initiated in step 1302, algorithm 1301 readsdefault calibration parameters from program memory 330 (FIG. 3).Algorithm 1301 then proceeds to step 1303.

[0291] In step 1303, algorithm 1301 executes detector offset calibrationalgorithm 584 and detector gain calibration 583 in order to calibrateoffsets 401-1 through 401-6 and amplifiers 404-1 through 404-6 tooptimally receive detector signals A_(R), B_(R), C_(R), D_(R), E_(R) andF_(R). Once OPU input parameters Offset and Gain are calibrated, spinmotor 101 can bring optical media 102 to a starting rotational speed atwhich point algorithm 1301 proceeds to step 1304.

[0292] In step 1304, algorithm 1301 executes FES Gain calibration 510 tocalibrate the FES Gain parameter to gain amplifier 509. At this point,focus loop 501 can be closed and algorithm 1301 then proceeds to step1305 where algorithm 1301 executes FES offset calibration 508,optimizing the FES Offset parameter to summer 507. Algorithm 1301 thenproceeds to step 1306 where algorithm 1301 executes TES offsetcalibration 542. Algorithm 1301 then executes TES gain calibration 544in step 1307. Algorithm 1301 then executes TES offset calibration 542again in step 1308. In some embodiments, TES offset calibration 542 andTES gain calibration 544 may alternately be executed until the values ofthe TES offset and the TES gain acceptably converge. Further, in someembodiments FES gain calibration 510 and FES offset calibration 508 maybe alternately executed until the FES gain parameter and the FES offsetparameters converge.

[0293] In the embodiment of algorithm 1301 shown in FIG. 13B, once theTES offset parameter has been re-calibrated in step 1308, algorithm 1301proceeds to step 1309 to execute focus loop-gain calibration 522.Tracking loop 502 is closed before algorithm 1301 executes trackingloop-gain calibration 585 in step 1310. Algorithm 1301 then proceeds tostep 1311, where TES/FES crosstalk gain calibration 579 is executed.Once TES/FES crosstalk gain calibration 579 is executed, algorithm 1301then executes focus loop gain calibration 522 in step 1312 and trackingloop gain calibration 585 in step 1313. In some embodiments, trackingloop gain calibration 585, focus loop gain calibration 522, and TES/FEScrosstalk gain calibration 579 can be sequentially executed until thecalibration parameters converge.

[0294] In step 1314, algorithm 1301 calibrates notch filters 519 and 551by executing notch calibration 520 and notch calibration 552. Again, insome embodiments of the invention, algorithm 1301 may proceed againthrough steps 1303 through 1314 until all of the resulting calibrationparameters have converged.

[0295] In step 1315, algorithm 1301 loads the new calibration parametersinto program memory 330. In some embodiments, program memory 330 is aflash memory. In some embodiments, the new parameters may be writtenonto optical media 102 so that optical media 102 can be started eachtime with these optimized parameters. Again, in some embodiments if thenew calibration parameters (operating parameters) of drive 100 differbeyond a threshold value from the old operating parameters, then the newcalibration parameters may not be stored or may not be stored to replacethe old operating parameters (the stored parameters). New calibrationparameters that vary significantly from the old operating parameters maybe stored until a new calibration operation is performed and, if the newcalibration parameters from the new calibration operation also varysignificantly, then the new calibration parameters may be stored. Insome embodiments, an average of the new calibration parameters and theold calibration parameters can be stored in order that operatingparameters not vary to quickly. In some embodiments, operatingparameters may be allowed to vary by a maximum amount so that if the newcalibration parameters differ from the old operating parameters by anamount over the maximum amount, than the old operating parameters variedby the maximum amount are stored in place of the new calibrationparameters. In some embodiments, the new calibration parameters arestored in a flash memory of program memory 330. In some embodiments,some of the operating parameters can be written onto optical media 102instead. Writing operating parameters onto optical media 102 directlycan be useful for storing parameters that closely depend on theparticular optical media.

[0296] In some embodiments of the invention, further calibrations mayalso be executed in algorithm 1301, including calibration 560 forcalibrating one-track jump algorithm 559, inverse non-linearitycalibrations 512 and 547, and calibrations related to decimation filters414-1 through 414-6.

[0297]FIGS. 14A and 14B show embodiments of step 1302 of FIG. 13.Algorithm 1302 calibrates OPU input parameters A, B, C, D, E and F bysetting the offset values of each of offsets 402-1 through 402-6 and thegain values of each of variable amplifiers 404-1 through 404-6. In someembodiments, step 1302 may include a calibration of decimation filters414-1 through 414-6 as well. The embodiment shown in FIG. 14A performs adark-current calibration of the OPU input parameters. The embodimentshown in FIG. 14B performs a calibration of the OPU input parameterswith light scattering present.

[0298] The embodiment of step 1303 shown in FIG. 14A starts with step1401 where parameters can be passed to step 1303. In some embodiments,the parameters include a gain parameter bFrontEndGain and a calibrationtype flag bCalTypeFlag. The gain parameters indicate the gains of eachof amplifiers 404-1 through 404-6. Algorithm 1303, then, includesaspects of detector offset calibration 584 and detector gain calibration583.

[0299] In some embodiments, the gains and offsets of gains 404-1 through404-6 and offsets 402-1 through 402-6 can be performed with laser off,i.e. a dark-current calibration. In some embodiments, the gains andoffsets of gains 404-1 through 404-6 and offsets 402-1 through 402-6 canbe performed with laser on and without optical media 102 in order toadjust for the presence of light scattering in OPU 103. FIG. 14Aillustrates a dark current calibration. FIG. 14B illustrates anadjustment to calibrate for light scattering.

[0300] In some embodiments, as shown in FIG. 14A, the gain of variableamplifiers 404-1 through 404-6 is fixed while the offset values ofoffsets 402-1 through 402-6 are calibrated. In some other embodiments,the gain of amplifiers 404-1 through 404-6 can also be adjustedaccording to a calibration criteria (for example that the dynamic rangeof the outputs from decimation filters 414-1 through 414-6 should be afixed peak-to-peak value).

[0301] In step 1402, algorithm 1302 switches to a high power mode. Inhigh power mode drive 100 is operational, as opposed to sleep mode.Operating voltages are brought to their operating values and power isavailable to laser 218 of OPU 103 and spin motor 101.

[0302] From step 1402, algorithm 1302 executes step 1404. In step 1404,algorithm 1302 determines the gains of each of amplifiers 404-1 through404-6 based on the gain parameter input at step 1401, bFrontEndGain. Insome embodiments, the gain of each of amplifiers 404-1 through 404-6 isset to bFrontEndGain. The value of the gains for each of amplifiers404-1 through 404-6 can be stored in a gain array 1414. In someembodiments, the parameter bFrontEndGain may include a different gainvalue for each of amplifiers 404-1 through 404-6. The gain parameters,then, can be set during a factory calibration or a re-work calibrationand stored in program memory 330. In some embodiments, the gain valuesfor each of amplifiers 404-1 through 404-6 are set to fill the operatingrange of digital to analog converters 410-1 and 410-2 (FIG. 4).

[0303] In step 1405 the laser is set on or off depending on thebCalTypeFlag parameter input during step 1401. If the laser is off, thenthe calibration is a dark current calibration, zeroing the output ofdecimators 414-1 through 414-6 when the laser power is off. Acalibration with laser 218 on can further eliminate systematic lightscattering in OPU 103.

[0304] In steps 1406 through 1411, the offset values for each of offsets402-1 through 402-6 is set. In some embodiments, the offset value is setso that the output signal from decimators 414-1 through 414-6 is zeroduring calibration. In a laser-on calibration, steps 1406 through 1411can, in some embodiments, be executed with a standard optical media 102in drive 100 to provide standard reflections. In some embodiments, nooptical media 102 is utilized or a light absorbing material insubstitution for optical media 102 can be utilized. Each of blocks 1406through 1411 updates part of an offset array 1415, which stores theoffset values for offsets 402-1 through 402-6. Algorithm 1303 then exitsin step 1413, indicating any error conditions that have occurred (suchas offset values out of range, laser failed to function, or command wasaborted, for example).

[0305]FIG. 14B shows an embodiment of an input signal offset and gaincalibration algorithm according to the present invention that includesoffsets for stray light. Detectors 225 and 226 (FIG. 2B) of OPU 103, forexample, receive light from laser 218 that has not been reflected fromoptical media 102. This “stray light” causes sensor offsets that canaffect tracking servo system 502 and focus servo system 501 (FIGS. 5Aand 5B). One particular issue is that when the power of laser 218 isshifted from read power to write power, for example, the amount of straylight measured at detectors 225 and 226 shifts, resulting in shifts inthe tracking error signal offset and focus error signal offsets thatoptimize operation of optical disk drive 100. In some cases, the shiftcan be large enough to cause a write abort condition to be indicated bywrite abort 537 or to cause writing of data with uncontrolled trackingerror signal offsets and focus error signal offsets.

[0306]FIG. 14B shows an embodiment algorithm 1302 that calibrates inputsignal offsets for read laser powers and write laser powers. Opticaldisk drive 100, then, can automatically shift input signal offsets so asto eliminate shifts in offset due to operating changes in the power oflaser 218.

[0307] In step 1450 of algorithm 1302, optical disk drive 100 is poweredfull on except that spin driver 101 is not operating. Further, opticalmedia 102 is removed from optical disk drive 100 so that no light isreflected back into OPU 103 from optical media 102. When optical diskdrive 100 is power on, all voltage levels are brought to operatingparameters and the drive is “awake” instead of in sleep mode.

[0308] In step 1451, input signal gains, e.g. the gains of each of gainadjusts 404-1 through 404-6, are calibrated in read mode. In someembodiments, the input signal gains for each of the input signals,signals A_(v), B_(v), C_(v), D_(v), E_(v) and F_(v) shown in FIG. 4, isset to constant values. In some embodiments, the input signal gains foreach of the input signals can be set so as to fill the dynamic range ofanalog-to-digital converters 410-1 and 410-2 when the read power levelis set.

[0309] In step 1452, the input signal gains can be set for a write powerlevel of laser 218. Again, the input signal gains can be set to constantlevels. Further, the input signal gains can be set in order to fill thedynamic rang eof analog-to-digital converters 410-1 and 410-2 when thewrite power level is set.

[0310] In step 1453, a dark current input offset calibration isperformed. An embodiment of this input offset calibration is shown inFIG. 14A.

[0311] In step 1454 the laser power of laser 218 is set at read power.In some embodiments, read power is set nominally at 0.25 mW.Additionally, the input sensor gains of gain adjustments 404-1 through404-6 are set for read power and other channel gains and offsets inpreamp 310 (FIG. 3) can be set for read operation. Further, input signaloffsets of offsets 402-1 through 402-6 can be zeroed. In step 1455,digitized values of the input signals (e.g., A_(f), B_(f), C_(f), D_(f),E_(f) and F_(f) in FIG. 4) are measured. In some embodiments, thedigitized values of the input signals are averaged over multiple samplesafter a time delay from setting the power level of laser 218. Forexample, the time delay can be about 10 msec. Additionally, 256 samplesof each of the digitized input signals can be acquired and averaged todetermine the stray light values. Input signal offsets for read powerlevels, then, can be set to values such that the digitized input signalsare a predetermined value, for example zero.

[0312] In step 1456, laser power and other channel parameters (e.g.,input signal gains and parameters of preamp 310) are set for write mode.In some embodiments, write laser power is nominally at about 1.1 mW. Insome embodiments, write laser power can be set at about 1.5 times readpower and input signal offsets for any other laser power can beinterpolated from the input signal offsets at these values. In somecases, the measured stray light is substantially linear with laserpower.

[0313] In step 1457, the input signal offsets for write power aremeasured. The input signal offsets of offset blocks 402-1 through 402-6can be zeroed and the digitized values of the input signals aremeasured. The input signal offsets appropriate for write operations areset such that the digitized values are at a predetermined value, forexample zero. Again, a time delay, for example of about 10 ms, can beexecuted before measurement of the digitized values. Again, an averageof the digitized input signals over many samples, for example 256, canbe utilized to set the input signal offsets.

[0314] In some embodiments, the read power level can be set nominally to0.25 mW and the write power level is nominally 1.1 mW. In someembodiments, two points are utilized in calibration, e.g. the read powerlevel and 1.5 times the read power level, and read and write offsets areinterpolated from these points.

[0315] Input signal offset values for no laser power (dark current),read powers, and write power can then be stored, for example in memories320 and 330 (FIG. 3). During operation of optical disk drive 100, inputsignal offsets appropriate for read operations are loaded when opticaldisk drive 100 is in read mode and input signal offsets appropriate forwrite operations are loaded when optical disk drive 100 is in writemode. In some embodiments, if other laser powers are set (for example, areduced laser power during multi-track seek operations) appropriateinput signal offsets can be determined by linear interpolations usingthe input signal offsets at read power and at write power. Whenswitching between read mode and write mode, the appropriate input signalparameters can be set in order to minimize transients in focus servosystem 501 and tracking servo system 502.

[0316] Frequent calibration of the dark current offset can correct forthermal drift of the analog electronics of drive 100. For example,offset calibration 1302 of FIG. 14A can be performed whenever focus isclosed. A method of calibration for thermal drift can include openingtracking and focus servos and shutting laser power off, measuring thedark current offsets by monitoring the digitized values output fromanalog to digital converters 410-1 and 410-2 or decimators 414-1 through414-6, and adjusting the stray light values for each of a read mode(i.e., with operating parameters set for read operations) and a writemode (i.e., with operating parameters set for write operations). Oncethe stray light values have been adjusted for the new dark currentoffset values, focus and tracking can be reacquired. In someembodiments, average dark current offsets can be measured. In someembodiments, detector inputs can be disabled and dark current samplescan be read while tracking and focus servo systems remain closed.

[0317] The write power stray light values can be measured duringmanufacturing at one know laser power, for example 1.1 mW. In someembodiments, an adaptive calibration is performed to adjust the laserpower to optimize write error rates. The actual write power duringoperation of drive 100, then, will vary. A stray light adjustmentalgorithm scales the stray light correction values based on the actualwrite laser power using a linear interpolation. These scaled write straylight values are added to the periodically measured dark offset valuesand stored whenever the dark offset values are measured. In write modedisk 100 utilizes the write values and in read mode disk 100 utilizesthe read values. Input offsets, then, are always accurate for the laserpower being used and transients in tracking servo system 502 and focusservo system 501 can be minimized. If stray light is not considered inthe input offset, tracking servo system 502 and focus servo system 501will experience shifts when laser power changes. With stray light offsetcalibration, a looser tolerance for stray light can be accommodated.

[0318]FIGS. 15A and 15B illustrate an embodiment of focus gaincalibration 510, which can be executed in step 1304 of calibrationalgorithm 1301 of FIG. 13. FIGS. 15A and 15B also illustrate calibrationof a focus sum threshold value. FIG. 15A shows a block diagram ofalgorithm 510 while FIG. 15B illustrates graphically signals andactuator motions initiated by focus gain calibration 510. In step 1501,algorithm 510 is called. In step 1502, default values for the FES gainof FES gain 509 and the FES offset of offset summer 507 are loaded. Aswas discussed above, the starting FES offset and FES gain parameters canbe input from optical media 102 in some embodiments and, in someembodiments, can be input from program memory 330.

[0319] In step 1503, algorithm 510 generates a focus control effort thatmoves OPU 103 sinusoidally from its present position to an extreme pointof OPU 103. The extreme point is the point furthest away or the pointclosest to optical media 102. This step is graphically illustrated inthe actuator position graph during time period 1. From the extreme pointof OPU 103, OPU 103 is sinusoidally moved to the opposite extreme andback to the extreme point in step 1504, as is indicated in time period 2in FIG. 15B. During this movement, the sum signal from summer 534 ismonitored. An example of the sum signal from summer 534 is shown in FIG.15B on the same time axis as is the actuator position signal. The peakvalues of the sum signal are also determined in step 1504. In someembodiments, the peak value of the sum signal is the average of the twopeak values measured as OPU 103 is moved from the first extreme positionto the opposite extreme position and back to the first extreme position.The peak sum signal and the sum of peak sum signals can be stored invariables 1507, along with a counter for the number of peak valuesstored.

[0320] In step 1505 of algorithm 510, a reasonable sum threshold iscalculated. The reasonable sum threshold is set based on the peak sumsignal calculated in step 1504. In some embodiments, the reasonable sumthreshold is set to be half of the peak sum signal calculated in step1504. However, any reasonable value can be utilized for the reasonablesum threshold (such as, for example, between about 30% to about 90% ofthe peak sum signal). As the reasonable sum threshold is lowered thefocus control becomes more lax. Conversely, as the reasonable sumthreshold is increased it becomes increasingly easier to lose focus. Thereasonable sum threshold is output to focus OK algorithm 536 and isfurther utilized to determine whether there is sufficient focus toindicate a focus closed condition to other algorithms executing on drive100.

[0321] From step 1505, algorithm 510 proceeds to step 1506. In step1506, algorithm 510 moves OPU 103 from the first extreme to the oppositeextreme and measures a focus control effort FCSOFFA that occurs at thethreshold indicated by the reasonable sum threshold value calculated instep 1505. Further, another sum threshold peak is measured to be addedto the sum peak variables 1507. In step 1508, algorithm 510 moves OPU103 back to the extreme position and measures a focus control effortFCSOFFB as the sum signal again crosses the threshold indicated by thereasonable sum threshold value. Again, the sum signal peak is tabulatedand recorded in variables 1507. A threshold in-focus control effort, theoffset control effort FCSOFF, then, can be calculated as the average ofthe two threshold control efforts FCSOFFA and FCSOFFB. The movement ofOPU 103 and the resulting sum signals as steps 1506 and 1508 areexecuted as is shown in FIG. 15B at times 3 and 4, respectively.

[0322] In some embodiments of algorithm 510, in particular thoseembodiments that are executed on microprocessor 432, algorithm 510controls OPU 103 through DSP 416. In step 1509, algorithm 510 frommicroprocessor 432 communicates the threshold value to DSP 416. DSP 416then monitors the sum signal from summer 507 and compares the sum signalto the calibrated threshold value to determine, for example, if focus isbad (e.g., algorithm 536), if focus can be closed (e.g., algorithm 535),or if a defect is detected (e.g., algorithm 591).

[0323] In step 1510, algorithm 510 moves OPU 103 to the positionindicated by the focus offset control effort FCSOFF calculated in step1508. In some embodiments, OPU 103 is moved to FCSOFF in a sinusoidalfashion in order to avoid exciting mechanical resonances which can beexcited with motions of OPU 103 that are not smooth.

[0324] Algorithm 510 then proceeds to step 1511. In step 1511, a smallersinusoidal perturbation around the FCSOFF control effort is applied tofocus actuator 206 in order to sinusoidally move OPU 103 about thethreshold focus position indicated by the reasonable sum threshold valueof the sum signal by a small amount (e.g., half the amplitude requiredto make the sum signal drop below the reasonable sum threshold). As OPU103 is oscillated about the threshold value, the FES signal output fromsummer is monitored. The FES signal can be sampled a number of times(e.g., 300 times) at each point and the FES peak maximum and FES peakminimum values can be stored in variables 1512. In some embodiments,step 1511 monitors the FES signal through four oscillations of OPU 103,however any number of oscillations can be monitored. FIG. 15B shows intime period 6 the sinusoidal movement of OPU 103 and the FES signal.

[0325] In step 1513, the average maximum value of the FES signal and theaverage minimum value of the FES signal through the oscillationsexecuted in step 1511 are calculated from variables 1512. Additionally,the average peak-to-peak value of the FES signal is calculated in step1513. Additionally, in some embodiments peak sum signals are added toprevious peak sum signals and a running total is stored.

[0326] In step 1514, a new gain value is calculated from the valuesobtained from the average peak-to-peak value of the FES signalcalculated in step 1513. In some embodiments, the gain is calculated sothat the average peak-to-peak value of the FES signal is a predeterminedvalue. In some embodiments, the gain is calculated so that the maximumand minimum peak-to-peak values are at a predetermined value. Once thegain value is calculated, step 1514 transfers the gain value throughmailboxes 434. In some embodiments, the calculations of steps 1513 and1514 can be performed by DSP 416. In some embodiments, the calculationsof steps 1513 and 1514 can be performed by microprocessor 432 with theFES peak values determined by DSP 416. In step 1514, the new gain valueis written to mailboxes 434 for transfer to DSP 416 or to microprocessor432, depending on which of DSP 416 or microprocessor 432 performs thecalculation.

[0327] Steps 1511, 1513, and 1514 can be repeated a number of times, forexample four times, in order to converge on the best calibrated gainvalues. In step 1515, microprocessor 432 updates sensor thresholdmailboxes 1515 with a value, for example, of half the average peak sumsignal to be implemented by focus servo algorithm 501. In step 1516, thenew gain values for FES gain 509 are stored, for example in programmemory 330. In step 1517, algorithm 510 moves OPU 103 away from opticalmedia 102 before exiting algorithm 510 in step 1518.

[0328]FIGS. 16A, 16B and 17 show embodiments of FES offset calibration508. In some embodiments, FES offset calibration 508 optimizes the FESOffset value for best servo operation, as shown in FIG. 16. In someembodiments, FES offset calibration 508 optimizes the FES Offset valuefor best read/write operation, which is shown in FIG. 17. In someembodiments, FES offset calibration 508 executes algorithm 508 shown inFIGS. 16A and 16B and algorithm 508 shown in FIG. 17 and calculates anFES offset calibration which compromises between optimum servo-systemconsideration and optimum read/write considerations. FIG. 16C shows agraph of the TES peak-to-peak signal as a function of FES offset curve.If the FES offset is enough to move off of the flat portion of thecurve, then the TES peak-to-peak signal will get smaller and the TESgain will need to change.

[0329]FIG. 16A shows an embodiment of focus offset calibration 508 thatincludes an optimum servo calibration. Algorithm 508 starts when calledat step 1601. In step 1602, algorithm 508 checks to be sure that focusservo algorithm 501 indicates that focus is closed and the spin servoindicates that optical media 102 is spinning. See the Spin Motor ServoSystem disclosures. If focus is not closed or optical media 102 is notspinning, then algorithm 508 returns after setting an error flag in step1607. If an abort condition is detected, then algorithm 508 exitsthrough step 1609 after setting an abort flag.

[0330] If both focus is closed and optical media 102 is spinning, thenalgorithm 508 proceeds to step 1603 where tracking is turned off. Whentracking is turned off, i.e. tracking servo algorithm 502 is not closed,then the TES signal becomes a sinusoidal signal as the tracks pass underOPU 103. In step 1604, the TES settings (including TES Gain and TESoffset values as well as the current tracking control signal) arestored. In step 1605, the TES gain is set to a default value (forexample 0×20) and the TES offset is set to 0. If algorithm 508 isprimarily executed on microprocessor 432, these parameters can becommunicated to DSP 416 in mailboxes 434 where DSP 416 monitors the TESsignal output from TES gain 543 during execution of algorithm 508.

[0331] In step 1606, FES offset is set to zero. In step 1608, algorithm508 monitors the peak-to-peak value of the TES signal output from TESgain 543 while decrementing the focus offset value. The focus offsetvalue is decremented by a set amount during each step. The TESpeak-to-peak value can be generated by TES P-P algorithm 545. Duringstep 1608, FES offset is decremented by a set amount and, if the TESpeak-to-peak value increases, then a best FES offset value is set to theFES offset value. If, during a set number of decrements, thepeak-to-peak TES signal decreases, then step 1608 stops decrementing andexits. In some embodiments, if a best FES offset value is located (i.e.,indicating that a peak in the TES peak-to-peak value versus FES offsetcurve has been located), then algorithm 508 proceeds to step 1612. Insome embodiments, once a peak in the TES peak-to-peak value is located,the focus offset value may be stepped through the peak with a finerincrement in order to better locate the peak and provide a better valueof the focus offset value. If an error is discovered (e.g., the TESpeak-to-peak value is below a threshold peak-to-peak value) thenalgorithm 508 can exit with an error-flag set at step 1607. If an abortcommand is received, algorithm 508 can exit with an abort indication instep 1609.

[0332] In some embodiments, or if a peak in the TES peak-to-peak curvehas not been located, algorithm 508 proceeds to step 1610, where the FESoffset value is reset to 0 or, in some embodiments, is set to the bestFES offset value.

[0333] In step 1611, algorithm 508 increases by a set amount the FESoffset value in order to determine if a maximum TES peak-to-peak valuecan be located in the increasing FES offset direction. Again, if themeasured TES peak-to-peak value is greater than the TES peak-to-peakvalue for the current best FES offset value, then the best FES offsetvalue is set to be the current FES offset value. In some embodiments ofthe invention, algorithm 508 in step 1611 can increment beyond a maximumin the measured TES peak-to-peak value by a number of increment stepswhere the TES peak-to-peak value decreases for each increment in the FESoffset value before exiting. Again, an error condition can be indicatedby exiting algorithm 508 through step 1607 and an abort condition can beindicated by exiting algorithm 508 through step 1609. Further, in someembodiments once a TES peak-to-peak value is located with the set amountof incrementation, a finer increment value can be utilized to moreaccurately find the TES peak-to-peak value. In some embodiments,algorithm 508 may search by incrementing the FES offset first and thendecrementing the FES offset second (e.g., reversing steps 1608 and 1611in FIG. 16A).

[0334] From step 1611 or step 1608, algorithm 508 proceeds to step 1612.In step 1612, the FES offset value output from FES offset calibrationcan be set to the best FES offset value. In step 1613, algorithm 508restores the TES gain and TES offset values that were saved in step1605. In step 1614, algorithm 508 restores tracking on (i.e., by closingtracking in tracking servo algorithm 502), provided that tracking was onin step 1602. Algorithm 508 exits at step 1615.

[0335]FIG. 16B shows another embodiment of FES offset calibrationalgorithm 508. Again, FES offset calibration algorithm 508 begins atstep 1601 with a call to FESOffsetCal. In step 1650, algorithm 508 makessure that voltages are brought to their operating levels (rather thanremaining in a sleep mode). Step 1652 represents the top of a loop whichends at return step 1615. Step 1653 traps an abort request. Theremainder of the embodiment of algorithm 508 shown in FIG. 16B is shownin state machine format. In state 1671, the focus offset value isinitialized to a starting value, for example 0×20. Algorithm 508 thenproceeds to state 1670. If optical media 102 is not spinning or focus isnot closed, then state 1670 starts optical media 102 spinning and closesfocus in focus servo algorithm 501, as shown in block 1602. Otherwise,state 1670 transitions based on the parameter bCalStep. In theembodiment shown in FIG. 16B, algorithm 508 can transitions to a measurebaseline state 1655, a measure coarse negative state 1659, a currentbest offset up state 1661, measure coarse positive state 1663, currentbest offset down 1665, measure fine 1667, or final loop gain calibrationstate 1678. On a failure or error condition, algorithm 1670 cantransition from state 1670 or from any other state to command retrystate 1672.

[0336] State 1672 can transition back to state 1670 to retry aparticular command a set number of times. If the current command is notsuccessfully completed within that set number of times, then algorithm508 can transition from state 1672 to command cleanup state 1673. Instate 1673, algorithm 508 performs cleanup functions to recover from thefailure or from an abort command and transitions to final flags state1676. If an abort command is detected, then algorithm 508 transitionsthrough state 1674 to abort state 1675. From state 1675, algorithm 508transitions to command cleanup state 1673.

[0337] State 1670 can transition to final flags state 1676 when bCalStepis set to Final Flags Step. In state 1676, algorithm 508 sets the exitflags. If an error is detected, then algorithm 508 can transitionthrough state 1656 to command retry state 1672. Otherwise, algorithm1676 transitions to command complete state 1677 for exit at return 1615.State 1677 can set error flags if errors are detected and can set a flagindicating successful completion if algorithm 508 was successfullycompleted.

[0338] In step 1670, if bCalStep indicates a measure baseline function,then algorithm 508 transitions to measure baseline state 1655. State1655 measures the baseline value of the TES peak-to-peak curve bycalculating the minimum and maximum value of the TES signal, as shown inblock 1658. If state 1655 indicates an error, then algorithm 508transitions through state 1656 to state 1672. If no error is indicated,the bCalStep is set to perform a coarse negative function and algorithm508 transitions through state 1657 back to state 1670.

[0339] If bCalStep is set to perform a coarse negative function, thenalgorithm 508 transitions from state 1670 to state 1659. In state 1670,algorithm 508 decrements the focus offset value to maximize the TESpeak-to-peak value. If a maximum value is found by decrementing thefocus offset value, then the focus offset value is set to that value. Insome embodiments, as shown in block 1660, a loop gain calibration offocus servo system 501 can be performed in state 1660. If state 1659indicates an error, then algorithm 508 transitions through state 1656 tostate 1672. Otherwise, bCalStep is set to current best offset up andalgorithm 508 transitions through state 1657 to state 1670.

[0340] In state 1670, algorithm 508 transitions to state 1661 ifbCalStep is set to current best offset. In state 1661, algorithm 508.State 1659 finds the best FES offset possible by decreasing the offset.State 1661 smoothly goes to the best offset found in state 1659. Ifstate 1661 indicates an error, the algorithm 508 transitions throughstate 1656 to state 1672. Otherwise, algorithm 1661 can set bCalStep tomeasure coarse positive and algorithm 508 can transitions through step1657 to state 1670. In some embodiments, a loop gain calibration onfocus servo loop 501 can be performed in state 1661 as indicated inblock 1662.

[0341] From state 1670, if bCalStep is set to measure coarse positive,then algorithm 508 transitions to state 1663. In state 1663 the best FESoffset can be found by increasing FES offset. If an error is detected instate 1663, then algorithm 508 transitions through state 1656 to state1672. Otherwise, bCalStep can be set to calculate the current bestoffset down and algorithm 508 can transitions through state 1657 tostate 1670. In some embodiments, a loop gain calibration can beperformed in state 1663 as indicated in block 1664.

[0342] If bCalStep is set to calculate the current best offset down,then algorithm 508 transitions to state 1665. In state 1665, algorithm508 smoothly goes to the best FES offset found in state 1663. If anerror is detected in state 1665, then algorithm 508 transitions throughstate 1656 to state 1672. Otherwise, algorithm 508 can set bCalStep tomeasure fine both ways and transition through state 1657 to state 1670.In some embodiments, a loop gain calibration of focus servo loop 501 canalso be performed in state 1665.

[0343] If bCalStep is set to measure fine bothways, then algorithm 508transitions from state 1670 to state 1667. In state 1667, algorithm 508starts at the best FES offset and gain determined by states 1659 and1663 and take fine steps, in both positive and negative directions, tofind a point where the TES peak-to-peak becomes significantly reduced.If an error is detected in state 1667, then algorithm 508 transitionsthrough state 1656 to state 1672. Otherwise, bCalStep can be set to loopgain cal and algorithm 508 can transition through state 1657 back tostate 1670.

[0344] If bCalStep is set to loop gain cal, then algorithm 508transitions from state 1670 to state 1678. In state 1678 a loop gaincalibration is performed on the focus servo system 501. bCalStep canthen be set to final flags and algorithm 508 can transition back tostate 1670.

[0345]FIG. 17 shows a focus offset calibration algorithm 508 thatprovides a best read/write focus offset value. Algorithm 508 of FIG. 17is a focus offset jitter calibration starting at step 1701. In step1702, algorithm 508 of FIG. 17 a seek operation is performed, forexample by performing multi-track seek algorithm 557, to position OPU103 over a section of optical media 102 which contains readable data.When step 1702 is complete, both focus servo 501 and tracking servo 502are closed.

[0346] In step 1705, algorithm 508 of FIG. 17 adjusts the Focus Offsetvalue. In step 1706, algorithm 508 adjusts the total open loop gain ofthe focus servo loop (i.e., with focus servo algorithm 501 and theplant) to provide a unity response at a crossover frequency. Thecrossover frequency is the frequency where the open loop transferfunction for the focus servo loop (i.e., including focus servo algorithm501 and the plant) is unity. In some embodiments, the crossoverfrequency is about 1.5 kHz. In step 1708, data jitter is measured.Additionally, jitter can be measured by monitoring the byte error ratein a read operation. In some embodiments, jitter can be measured bycomparing the phase measurement from slicer 422 (FIG. 4) with the syncmark detector of block 426 (FIG. 4), for example.

[0347] In step 1709, algorithm 508 checks to see if the data jitter hasbeen minimized. If not, then algorithm 508 returns to step 1705 toadjust FES offset further. Otherwise, in step 1710 algorithm 508 setsFES offset to the optimum value and exits in step 1711.

[0348]FIGS. 18 and 19 show an embodiment of TES Offset Calibration 542which may be executed in steps 1306 and 1308 of calibration algorithm1301 of FIG. 13. Again, TES Offset calibration 542 may include either anoffset calibration based on optimum servo operation, as is shown in FIG.18, or an offset calibration based on optimum read/write operation, asis shown in FIG. 19. In some embodiments, offset calibration 542 mayinclude embodiments based both on best servo operation and bestread/write operation and may provide a TES Offset value that is acompromise between the TES offset based on best servo operation, as isshown in FIG. 18, and the TES offset based on optimum read/writeoperation, as is shown in FIG. 19. The compromise tracking error signaloffset, for example, can be a weighted average between the TES offsetthat optimizes servo function and the TES offset that optimizes readfunction. Changing the TES offset often means that OPU 103 is nottracking over track centers, but off the track center. Therefore, drive100 may be less stable. For example, a bump in one direction may moreeasily lose tracking. Additionally, other parameters, for exampletracking loop gain, may be incorrect for the particular TES offset.

[0349] In FIG. 18, TES offset algorithm 542 is initiated at step 1801where it is called. In step 1802, algorithm 542 checks whether focus isclosed in focus servo algorithm 501 and that spin motor 101 is spinning(see the Spin Motor Servo System disclosures). If an error is detected(for example if focus is on but optical media 102 is not spinning), thenalgorithm 542 exits through step 1808 while setting an error flag. Errorrecovery routines are further described in the System Architecturedisclosures. If an abort condition is detected, then algorithm 542 exitsthrough step 1809 indicating an abort.

[0350] Algorithm 542 then proceeds to step 1803. In step 1803, iftracking is on algorithm (i.e., tracking servo system 502 is closed),542 proceeds to step 1804 to shut tracking off. Once tracking is off,algorithm 542 proceeds to step 1805. In step 1805, the current TES gainand the current TES offset are saved. In step 1806, the TES offset valueis set. In some embodiments, the TES offset can be set to zero. In otherembodiments, the TES offset may be left at the current TES offset valueor may be set at another default value. In some embodiments, algorithm542 may also reset the TES gain value at step 1806 to a default value.In some embodiments, the TES gain value is left at the current TES gainvalue. Algorithm 542 then proceeds to step 1807.

[0351] In step 1807, algorithm 542 checks to be sure that focus servoalgorithm 502 indicates a focus closed condition. If focus is lost, thenalgorithm 542 can exit through step 1808 indicating an error message.Again, if an abort condition exists, then algorithm 542 can exit throughstep 1809. Algorithm 542 then proceeds to step 1810.

[0352] In step 1810, algorithm 542 determines the minimum and maximumvalues of the TES signal. Since tracking is off, the TES signal is asinusoidal signal that transitions a period of the sine wave as a trackpasses beneath OPU 103. From averaging the minimum and maximum values,the center of the sinusoidal TES signal can be determined. This measuredTES offset signal can be stored as variable s_1SignalOffset. In someembodiments, the average minimum and maximum values over a number ofperiods of the TES signal can be utilized to determine the measured TESoffset signal.

[0353] In step 1811, algorithm 542 checks whether the measured TESoffset value is zero. If it is, then in step 1812 a counter is set toiCalNum+1. If not, then iCount is incremented and algorithm 542 proceedsto step 1813. In step 1813, an offset is set to the TES offset minus themeasured TES offset. In step 1814, the calculated offset is truncated.In step 1815, the TES offset is set to the offset value calculated instep 1814. In step 1816, the counter iCount is checked to determine ifit is less than iCalNum+1. If so, then algorithm returns to step 1807.In step 1807, if iCount is equal to iCalNum then a time-out errorcondition can be set and algorithm 542 can exit through step 1808.

[0354] If iCount is greater than iCalNum, indicating that an optimum TESoffset value has been found, then algorithm proceeds to step 1817 wherethe optimum TES Offset value is stored. The TES gain value is also resetin step 1817. In step 1818, algorithm 542 closes tracking in trackingservo algorithm 502 if tracking was on when algorithm 542 was called.Algorithm 542 can then exit normally through step 1819.

[0355]FIG. 19 shows a TES offset calibration algorithm 542 that sets theTES offset based on optimum read/write conditions. Algorithm 542 asshown in FIG. 19 is called at step 1901. In step 1902, OPU 103 isposition over readable data on optical media 102. In some embodiments,OPU 103 is positioned over the middle of the optical media 102. In someembodiments, OPU 103 is positioned over optical media 102 andmulti-track seek algorithm 557 is utilized to position OPU 103 overreadable data on optical disk 102. In step 1903 algorithm 542 closesfocus in focus servo algorithm 501 and in step 1904 algorithm 542 closestracking in tracking servo algorithm 502.

[0356] In step 1905, algorithm 542 adjusts the TES offset value. The TESoffset value may be incremented in either direction (i.e., increasing ordecreasing). If incrementing the TES offset value in the first directionis not successful, then algorithm 542 can increment the TES offset valuein a second direction. Further, the starting TES offset value may be theoptimum TES offset value calculated by algorithm 542 as shown in FIG.18.

[0357] In step 1906, the TES gain is set to provide a total open-loopgain of unity at a TES crossover frequency. The TES crossover frequencyis the frequency that the open loop gain is set to unity. In someembodiments, the TES crossover frequency is about 1.8 kHz. In step 1907,data jitter is measured. Data jitter can be measured as described withstep 1708 of FIG. 17. In step 1908, algorithm 542 checks to see if thedata jitter determined in step 1907 is at a minimum. If not (i.e., ifthe data jitter continues to decrease as TES offset is incremented),then algorithm 542 returns to step 1905.

[0358] An optimum TES offset value can be determined when data jitterhad been decreasing with additional TES offset increments but now isincreasing. If an optimum TES offset value has been located, algorithm542 proceeds to step 1909 where the TES offset value is stored.Algorithm 542 can then exit at step 1910.

[0359]FIG. 20 shows an embodiment of TES gain calibration 544, which canbe executed in step 1307 of calibration algorithm 1301 shown in FIG. 13.Algorithm 544 is called at step 2001 and proceeds to step 2002. Aninitial value of the TES gain can be passed to algorithm 544. Theinitial value can be the current value of the TES gain or a defaultvalue of the TES gain. In step 2002, algorithm 544 determines that focusis closed in focus servo algorithm 501 and that optical media 101 isspinning. If focus is not closed or optical media 101 is not spinning,algorithm 544 exits with an error flag set in step 2006. If an abortcondition is detected during step 2002, algorithm 544 exits with anabort flag set through step 2007. If step 2002 exits normally, algorithm544 proceeds to step 2003. In step 2003, if tracking is on, algorithm544 proceeds to step 2004 to turn tracking off and then proceeds to step2005, else algorithm 544 proceeds to step 2005. In some embodiments, OPU103 can be positioned over a particular zone or a particular media typeon optical medium 102 in step 2002.

[0360] In step 2005, algorithm 544 checks for a focus closed condition(a focus closed condition can be indicated by the focus OK flag set byfocus OK algorithm 536). If focus has opened, then algorithm 544 canexit with an error flag through step 2006. Again, if an abort conditionis detected, algorithm 544 can exit with an abort flag set through step2007. If focus is closed and no error or abort conditions are detected,then algorithm proceeds to step 2008.

[0361] In step 2008, algorithm 544 determines the minimum and maximumvalues of the TES sinusoidal signal. Step 2008 may include TES P-Palgorithm 545. In particular, algorithm 544 determines the peak-to-peakvalue s_1PeakPeak of TES. In step 2009, a gain factor is calculatedbased on the peak-to-peak value determined in step 2009 and a referencepeak-to-peak value TES_GAIN_REF. In some embodiments, the gain factor isa ratio between the reference peak-to-peak value and the measuredpeak-to-peak value of the TES signal. In step 2010, algorithm 544 checksto be sure that the gain factor is between a lower and upper limit, forexample between 0.25 and 4, to insure that the TES gain is not variedtoo quickly or too slowly. If the gain factor is outside of the range,then the gain factor can be reset to be the extreme value in the range.

[0362] In step 2011, a gain value is set to the TES gain times the gainfactor. In step 2012, algorithm 544 checks to be sure that the gainvalue is between set limits (for example between -128 and +128). If theTES gain (the gain value) is outside of the set limits, then an errorflag can be set. Otherwise, the TES gain is set to the gain value instep 2013 and algorithm 544 proceeds to step 2014.

[0363] In step 2014, if counter iCount is less than a maximum and thegain factor is not 1, then algorithm 544 returns to step 2005. In step2005, iCount is incremented and an error condition may be set resultingin algorithm 544 exiting through step 2006 if iCount is the maximumiCount. If the gain factor is one, then algorithm 544 has converged on aTES gain value and proceeds to step 2015. In step 2015, algorithm 544turns tracking on if it was on when algorithm 544 started in step 2001and exits normally at step 2016.

[0364]FIG. 21 shows a loop gain calibration algorithm 2100 which can beeither focus loop gain calibration 522 executed in step 1309 ofcalibration 1301 of FIG. 13 or tracking loop gain calibration 562executed in step 1310 of calibration 1301 of FIG. 13. Both focus loopgain calibration 522 and tracking loop gain calibration 562 operate inessentially the same fashion. In focus loop gain calibration 522 a sinewave disturbance at the desired cross-over frequency is generated insine wave generator 528 and applied through summer 523 to the focuscontrol effort. A discrete Fourier transform from DFT 527 of the focuscontrol effort before summer 523 is compared with a discrete Fouriertransform from DFT 525 of the disturbance in gain calculation 526 todetermine the gain of loop gain amplifier 524 so that the overall openloop gain at the cross-over frequency is 0 dB. Similarly, in trackingloop gain calibration 562 a sinusoidal disturbance at a trackingcross-over frequency (which, in general, can be different from the focuscross-over frequency) is generated by a sine wave generator 568 andapplied to the tracking control effort through summer 563. A discreteFourier transform from DFT 567 of the tracking control effort beforesummer 523 is compared with a digital Fourier transform from DFT 565 ofthe disturbance is compared in gain calculation 566. The gain of loopgain 564 can be set so that the tracking total open loop gain is 0 dB.In some embodiments, the cross-over frequency for focus loop calibration522 can be about 1.5 kHz and the cross-over frequency for tracking loopgain calibration 562 can be about 1.8 kHz.

[0365] In FIG. 21, loop gain algorithm 2100 represents the generalizedloop gain calibration algorithm which can be executed as focus loop gaincalibration 522 or tracking loop gain calibration 562. Algorithm 2100 isstarted at step 2101 when it is called. Algorithm 2100 then proceeds tostep 2102. In loop gain algorithm 2100, the loop that is currently beingcalibrated is closed. In some embodiments, focus loop gain calibration522 can be executed without closing tracking. However, for tracking loopgain calibration 562 both focus and tracking are closed.

[0366] In step 2102, algorithm 2100 executes a Bode algorithm at thecrossover frequency. An embodiment of the Bode algorithm is furtherdescribed in FIG. 22. In essence, the Bode algorithm executed in step2102 disturbs the loop at the frequency indicated (in step 2102 at thecrossover frequency), performs a discrete Fourier transform (DFT) onboth the disturbance and the resulting measured signal, compares the twotransforms, and returns gain values for the indicated frequency withinthe range of frequencies. Therefore, in step 2102 the Bode algorithmreturns the total loop gain at the crossover frequency.

[0367] Once the loop gain at the crossover frequency is obtained in step2102, it is inverted in step 2103 and multiplied by the current gainvalue from block 2105 in step 2104 to form the new loop gain value. Thenew loop gain value is the gain value required so that the loop gain ofthe output signal from loop gain amplifier (amplifier 524 in focus loopgain 522 or amplifier 564 in tracking loop gain 562) at the crossoverfrequency is, for example, 0 dB. In some embodiments, in order to obtaina larger dynamic range with a limited number of available bits, the gainof the loop gain amplifier is segregated into a gain and a shift term.The total gain being the gain * 2 ^(shift). Therefore, in someembodiments algorithm 2100 spreads the new loop gain value into a gainand a shift term in step 2106. For example, in some embodiments data issent in 16 bit words and the loop gain value can be segregated into a 12bit gain term and a 4 bit shift term. A much larger dynamic range can berealized with only a slight loss in resolution. In step 2107, algorithm2100 saves the new gain of the loop gain amplifier. Algorithm 2100 exitsnormally in step 2108.

[0368]FIG. 22 shows an embodiment of a GetBode algorithm 2200 which canbe executed in step 2102 of loop gain calibration algorithm 2100 of FIG.21. In general, a Bode algorithm determines the frequency response ofany pair of signals in a servo loop by disturbing the loop (for exampleat summer 523 or 563 in FIG. 1) with a known disturbance and measuringthe response of the loop to that disturbance. Bode algorithm 2200 startswhen called at step 2201. Several parameters can be passed to Bodealgorithm 2200, including a start frequency and an end frequency, aparameter indicating which loop to disturb (either tracking or focus),an oscillator amplitude value (which may be different for tracking servoloop or focus servo loop), the number of averages to compute, whether ornot notch filters in the loop will remain active during the calibration,whether or not tracking must stay closed during the calibration, whetherautogain is turned on or off, and whether to use floating or fixed pointmath. Step 2202 indicates an initialization step. Step 2203 indicatesthe top of a loop, which finishes when the calibration sequence ofalgorithm 2200 is completed.

[0369] The remainder of algorithm 2200 is shown in state diagram format.From step 2204, algorithm 2200 enters introduction state 2217 wheresoftware pointers are initialized to point to the variables representingthe transfer functions numerator and denominator (e.g., TES, FES, andTracking Control Efforts). Additionally, introduction state 2217 turnsoff auto jump back if it is enabled. From introduction state 2217,algorithm 2200 enters a memory allocation state 2204. In memoryallocation state 2204, algorithm 2200 allocates sufficient memory toperform the Bode calculation of algorithm 2200. In some embodiments,allocation of memory can be done separately for each frequency becausethe trace length can be different for each frequency. A trace lengthinversely proportional to the frequency can yield better frequencyresolution.

[0370] If insufficient memory is available, algorithm 2200 transitionsto free memory state 2214 where any memory which is already allocated isfreed. From free memory state 2214, algorithm 2200 transition cantransition back to state 2214 if Bode calculations are to be done onfurther frequencies or to calibration finished state 2215, which closesthe loop started in step 2203, if the calculation is finished. If thereis not sufficient memory available to perform the calculation, algorithm2200 can exit at step 2216, indicating an insufficient memory errorcondition.

[0371] If state 2204 allocates sufficient memory, then algorithm 2200transition to state 2205. In state 2205, algorithm 2200 tests to insurethat focus is closed and, if indicated, tracking is closed. If focus isopen, then state 2205 closes focus. If tracking is open and should beclosed, then state 2205 closes tracking. If there is not enough memory,algorithm 2206 can transition to free memory state 2215 to freeadditional memory.

[0372] Once the requested loops are closed in state 2205, algorithm 2200transitions to state 2206. In state 2206, an oscillator operating at aselected frequency is turned on. On the first pass through algorithm2200, the selected frequency is the start frequency. On subsequentpasses, the selected frequency is between the start frequency and theend frequency. The oscillator applies a sinusoidal disturbance to thefocus or the tracking loop, as indicated. The amplitude of thedisturbance depends on previous measurements. For example, if there is apositive slope in the response data the amplitude can be decreased andif there is a negative slope the amplitude can be increased. Algorithm2206 then transitions to either state 2207 if an auto-gain is set on orto collect samples 2208 if auto gain is set off. If auto-gain is on, thedisturbance amplitude is adjusted so that the maximum peak-to-peakvalues for TES and FES are sufficiently close to a target value. Ifeither TES or FES are too large, the disturbance amplitude is decreased.If both are too small the disturbance amplitude is increased. In someembodiments, TES and FES can be monitored directly for frequencies belowa threshold frequency, for example about 8kHz, while the peak-to-peakvalues are monitored at frequencies above this frequency. Autogain state2207 can be looped with validate samples 2210 to ramp up the disturbanceamplitude. In validate samples state 2210, algorithm 2200 verifies thatfocus is still closed and, if required, tracking is still closed.Algorithm 2200 transitions through the loop including state 2207 and2210 until the amplitude of the disturbance generated in state 2206 isset. When complete, algorithm 2200 transitions to state 2208.

[0373] In state 2208, trace data is taken. Trace data includes data withthe disturbance and data measured from the control effort. As anexample, state 2206 may turn sine wave generator 528 on and state 2208then collects trace data from the input signal to summer 523 and tracedata from the output signal from summer 523, trace 1 and trace 2,respectively. Once trace data for both trace 1 and trace 2 is taken fora sufficient amount of time, algorithm 2200 transitions to state 2209.

[0374] In state 2209, the disturbance turned on in state 2206 is shutoff and algorithm 2200 transitions to state 2210. In state 2210,algorithm 2200 verifies that focus is still closed and, if required,tracking is still closed. In some embodiments, algorithm 2200 can alsocheck whether trace data in trace 1 and trace 2 has a sufficientpeak-to-peak amplitude. If trace data is not valid, for example becauseloops have opened, then algorithm 2200 transitions to state 2211. Instate 2211, algorithm 2200 attempts to repeat the measurement of thetrace data. If focus or tracking loops have opened, then the amplitudeof the sinusoidal disturbance started in state 2206 can be decreased.Once algorithm 2200 has adjusted parameters (e.g., the amplitude of thesinusoidal disturbance), then algorithm 2200 transitions back to state2205. If too many retries have been attempted, then algorithm 2200 cantransition to state 2213 and set an error flag.

[0375] If algorithm 2200 finds valid data in state 2210, algorithm 2200transitions to state 2212. In state 2212, the amplitude of both trace 1and trace 2 data at the frequency of the sinusoidal disturbance iscalculated. Once the calculations are completed in state 2212, algorithm2200 transitions to state 2213. In state 2213, the ratio between theamplitude of trace 1 to the amplitude of trace 2 is calculated.Algorithm 2200 then transitions to state 2214. Algorithm 220 can freethe memory utilized in the previous calculation. If an error flag hasbeen set or if the Bode calculation is complete, then algorithmtransitions to state 2215 and then finishes at state 2216. Otherwise,algorithm 2200 increments the frequency and transitions to state 2204 toallocate memory for the calculation at the next frequency.

[0376]FIG. 23 shows an embodiment of a discrete Fourier transformalgorithm 2300 (DFT) that can be utilized with Get Bode algorithm 2200of FIG. 22. DFT algorithm 2300 can be utilized anywhere, for example inDFT algorithms 527, 525, 567, and 565. In some embodiments, fixed pointmath can be utilized to execute the calculations described. In someembodiments, floating point math can be executed. Although algorithmsexecuted with fixed point math can be much faster, algorithms executedwith floating point math are more accurate and less prone to overflowproblems.

[0377] Algorithm 2300 starts when called at step 2301. In step 2302,variables R and I are initialized. In step 2303, further variablesRealComp and ImagComp are set to zero and the trace pointer is set to 0.In step 2304, algorithm 2300 checks to see if the sine and cosinecoefficients (R and I) exist for the current point on the traceindicated by the trace pointer. If not, then the sine and cosinecoefficients R and I can be computed in step 2305. Otherwise, algorithm2300 proceeds to step 2306. In step 2306, algorithm 2300 checks for amissed sample to assure that it keeps the sine and cosine sampleinstants time aligned with the measured waveforms time instants. If asample is missed in the measurement, then the algorithm must skip asample in the sine and cosine coefficient before performing the product.If not, then algorithm 2300 accumulates the product of the trace withthe sine and cosine coefficients in step 2307. Additionally, the tracepointer can be incremented in step 2307. In step 2308, the pointers tothe sine and cosine coefficients are incremented. In step 2309, if thereis more trace data, algorithm 2300 returns to step 2304. If all of thetrace data has been processed, then algorithm 2300 proceeds to step 2310where the amplitude of the accumulation computed in step 2307 iscomputed. In step 2311, the amplitudes are accumulated. In step 2312, ifthere are more averages to be processed, algorithm 2300 proceeds to step2303. Otherwise, algorithm 2300 computes the average amplitude in step2303 and exits at step 2314.

[0378]FIG. 24 shows an embodiment of TES-to-FES Cross Talk GainCalibration algorithm 579. As shown in FIGS. 5A and 5B, cross-talk gaincalibration 579 disturbs the tracking control effort by adding in asinusoidal disturbance from sinewave generator 581 to summer 563.Crosstalk Gain calibration 579 then measures the FES output fromcross-talk summer 513, calculates the single point DFT at thedisturbance frequency, and adjusts a gain in ratio calculation 582,which normalizes the frequency component in FES to the output of sinewave generator 581, in order to minimize the frequency component presentin FES. The frequency of the perturbation induced by sine wave generator581 is is chosen to provide the best overall calculation. In general,crosstalk is not a strong function of frequency. Therefore, whateverfrequency that is convenient (i.e. stable) can yield good results. Insome embodiments, one of the cross-over frequencies can be utilized, forexample 1.5 kHz or 1.8 kHz.

[0379]FIG. 24 shows a block diagram of an algorithm for performingcrosstalk calibration 579. Before executing crosstalk calibration 579,focus and tracking are both on. Algorithm 579 is called in step 2401with both focus and tracking on. In step 2402, algorithm 579 initializesvariables. In step 2403, algorithm 579 starts a loop that finishes whenalgorithm 579 determines that calibration of the crosstalk gainparameter to cross-coupling gain 514 is determined.

[0380] The remainder of algorithm 579 is shown in state function format.In state 2404, algorithm 579 allocates sufficient memory to perform thealgorithm. If sufficient memory is not available, algorithm 579transitions to step 2409 which frees any memory that has been allocated.Algorithm 579 then transitions to step 2410 where the loop started instep 2403 is terminated. Finally, algorithm 579 exits with an error flagset at step 2411.

[0381] If there is sufficient memory so that algorithm 579 allocatesmemory in state 2404, then algorithm transitions to state 2405. In state2405, algorithm 579 sets an initial crosstalk gain that can be utilizedin cross-coupling gain 514 (FIG. 5A). Algorithm 579 can set the initialcrosstalk gain by reading default values from a default file or byreading the last crosstalk gain value from program memory 330 or byreading the last crosstalk gain value utilized with optical media 102from optical media 102. Further, the best cross-talk gain value is setto the initial cross-talk gain variable. Once the initial value of thecrosstalk gain parameter is set, algorithm 579 transitions to state2406.

[0382] In state 2406, algorithm 579 performs a Bode calculation by, forexample, calling GetBode algorithm 2200 of FIG. 22. GetBode algorithm2200 inputs a disturbance into the tracking loop at the desiredfrequency, for example at the tracking crossover frequency (e.g., 1.8kHz). GetBode algorithm 2200, as executed in state 2406, measures theFES output from summer 513, and calculates the amplitude of the FES atthe disturbance frequency. The returned value from the Bode Calculationperformed within state 2406, then, is the signal component amplitude atthe frequency of the disturbance. If the amplitude is lower at thiscrosstalk gain than the lowest so far, then the best crosstalk gainvariable is set to the gain value. If the crosstalk does not have asmaller amplitude at the present crosstalk gain value, then algorithm579 transitions to state 2407.

[0383] In state 2407, algorithm 579 increments or decrements thecross-talk gain and returns to state 2406. In some embodiments,algorithm 579 may start at an initial gain and increment through a rangeof gains in order to determine the best cross-talk gain. In someembodiments, algorithm 579 can start at an initial gain and move thegain in a first direction. If the cross-talk is increased by a move inthe first direction, then algorithm 579 can move the cross-talk gain inthe opposite direction from the first direction until a cross-talk gainthat provides a minimum amount of TES-FES cross-talk is found. In someembodiments, algorithm 579 can search well beyond a located minimum (forexample about 5 increments) to insure that the located minimum isactually a minimum.

[0384] In state 2406, when algorithm 579 discovers that it has checkedeach gain value or if a gain value that results in a minimum amount ofcross-talk has been found, state 2406 transitions to state 2408. Instate 2408, algorithm 579 stores the new cross-talk gain value andtransitions to state 2409. In state 2409, algorithm 579 frees the memoryallocated in state 2404 and transitions to state 2410. In state 2410,algorithm 579 ends the search loop and exits normally at step 2411.

[0385]FIG. 25 shows an embodiment of a notch filter calibrationalgorithm 2500. Algorithm 2500, for example, can be notch filtercalibration 552 in tracking servo algorithm 502 or notch filtercalibration 520 in focus servo tracking algorithm 501. Notch calibrationalgorithm 2500 is called in step 2501. In step 2502, algorithm 2500performs a Bode calculation by, for example, calling Get Bode algorithm2200 of FIG. 22 in order to obtain the frequency response curve of theappropriate control loop within a particular frequency range. Thefrequency response curve indicates the amplitude of the discreet Fouriertransform at selected frequencies within the frequency range. In someembodiments, Get Bode algorithm 2200 of FIG. 22 provides ratios ofsingle point DFTs at discrete frequencies in the frequency range. Forexample, notch calibration 520 can calibrate notch filter 519 in therange of about 3 to about 5 kHz. Get Bode algorithm 2200 returns anarray providing the amplitude of the frequency response for, forexample, the focus servo loop or the tracking servo loop. In step 2503,algorithm 2500 locates maximum peaks in order to determine thefrequencies at which maximum responses are obtained. In some embodimentsof the invention, peaks over a threshold value are targeted so thatfrequencies corresponding to responses above a certain amount are found.In some embodiments, a certain number of peaks are found, regardless ofthe magnitude of the actual response. The frequencies at which maximumresponses are obtained are passed out of routine 2500, for example to anotch filter which filters the control signal at those frequencies.Algorithm 2500 then exits at step 2504.

[0386] If notch calibration algorithm 2500 is being executed as notchcalibration 520, then the Bode algorithm 2500 disturbs the focus controleffort and reads the responsive FES signal at the output of phase lead518. The frequencies at which maximum responses are measured are passedto notch filter 519 so that a notch filter can be established aroundthose frequencies. If notch calibration algorithm 2500 is being executedas notch calibration 552, then the Bode algorithm 2500 disturbs thetracking control effort and reads the responsive TES signal at theoutput of phase lead 550. The frequencies at which maximum responses aremeasured are passed to notch filter 551.

[0387] In some embodiments, focus is closed before algorithm 2500 iscalled as notch calibration 520. In some embodiments, focus and trackingare closed before algorithm 2500 is called as notch calibration 552.

[0388]FIG. 26 shows an embodiment of a feed-forward algorithm 2600.Feed-forward algorithm 2600 can be utilized as feed-forward block 532 infocus servo algorithm 501 and feed-forward block 579 in tracking servoalgorithm 502. Feed-forward algorithm 532 monitors the focus controleffort output from multiplexer 531 for harmonic variations which, forexample, can be the result of warping of optical media 102, bearing wearof spin motor 101, or other factors which can cause a periodic variationin the FES signal. Similarly, feed-forward algorithm 579 monitors thetracking control effort for periodic variations. Once detected, theperiodic variation in the FES signal can be anticipated by feed-forwardalgorithm 532 and OPU 103 can be moved with the same periodicity and anappropriate amplitude so that the periodic variation is effectivelyremoved from FES. Similarly, periodic variations in TES can beanticipated by feed-forward algorithm 579 and control arm 104 can bemoved periodically to remove these variations from TES.

[0389] Therefore, when operating fully and settled, feed-forwardalgorithm 532 and feed-forward algorithm 579 monitors the focus controleffort and the tracking control effort and provide periodic controlefforts that result in the removal of the effects of the anticipatedmotion from the FES and TES signals, respectively.

[0390] In some embodiments, algorithm 2600 removes periodic variationswhich are harmonics of the spin frequency of optical media 102 (i.e., ofthe rotation frequency of spin motor 101). Therefore, the output signalfrom algorithm 2600, the period variations, can be expressed as Asincot+Bcoscot, where co is the rotation frequency of spin motor 101. Theoutput signal from feed-forward algorithm 532, then, is input to summer533 and the output signal from feed-forward algorithm 579 is input tosummer 578.

[0391] Turning to algorithm 2600 of FIG. 26, a square-wave clock signalis provided which has a frequency equal to the frequency of spin motor101 times the length of a sine-wave look-up table utilized to generatethe sine wave. A delay parameter is also passed to algorithm 2600 whichdetermines the number of clock cycles to delay before re-sampling theinput signal and updating the parameters of the output signal fromsummer 2616. Further, the number of cycles to sample is input toalgorithm 2600.

[0392] The input signal is received by multipliers 2602 and 2603. Ingeneral, the input signal is of the form

f(t)=asinωt+bcosωt+g(t)

[0393] where a and b are the coefficients of periodic control effort yetto be removed from the control effort and g(t) is the control effortwhich does not include a component of the spin-motor frequency. Uponstartup, the entire amount of the periodic correction can be included inthe input signal f(t) and therefore a=A and b=B. During operation, smallcorrections on the output parameters A and B are included in the inputsignal f(t).

[0394] The input signal f(t) is multiplied by sin(ωt) in multiplier 2602and multiplied by cos(ωt) in multiplier 2603. The output signal frommultiplier 2602, f(t)sinωt, is input to multiplexer 2609 and the outputsignal from multiplier 2603, f(t)cosωt, is input to multiplexer 2608.

[0395] Countdown timer 2605, can be loaded with the delay parameter and,on each clock cycle, counts down. During the delay period, countdowntimer 2605 outputs a select signal that selects the grounded input tomultiplexers 2609 and 2608. Once countdown timer 2605 reaches zero(indicating the end of the delay period), then timer 2605 outputs aselect signal to multiplexers 2609 and 2608 which selects the outputsignals from multipliers 2602 and 2603, respectively.

[0396] The output signals from multiplexer 2609 and 2608 are input tosummers 2610 and 2611, respectively. Summer 2610 sums its input with itsoutput. Summer 2610 starts each sampling period with a zero'd outputsignal. Between the end of the delay period and the end of the sampleperiod set by the signal DFTCYCLES, summer 2610 sums the signalf(t)sinωt over DFTCycles of periods of the sine wave. Therefore, at theend of that summation, the output signal from summer 2610 is related tothe coefficient a, all other products in f(t) being zero'd due to thesummation. Similarly, summer 2611 sums f(t)cosωt over DFTCYCLES numberof periods so that the output signal from summer 2611 is related to thecoefficient b.

[0397] The number of cycles DFTCYCLES times the length of the sinetableis calculated in multiplier 2606 and summed with the delay in summer2607. Countdown timer 2617, then, counts down over the delay and theperiod in which summers 2610 and 2611 are accumulating. At the end ofthe countdown period, countdown timer 2617 enables summers 2612 and 2613before starting the next period. During the period when summers 2612 and2613 are enabled, the output signal from summers 2610 and 2611,respectively, are added into the values already present. Summers 2612and 2613, then, hold the output values until, once again. summers 2610and 2611 are finished accumulating. The output signals from 2612 and2613 are multiplied by the sine function and the cosine function,respectively, and added in summer 2616 to provide an output signal ofthe form Asinωt+Bcosωt, which is added to the control effort. Thecoefficients A and B are updated on each accumulation period. Eachaccumulation period, essentially, takes a single point DFT of the inputsignal to determine the ωfrequency component of the input signal andoutputs that component.

[0398] In some embodiments of the invention, the calibrated parametersare different for different track locations on optical media 102. Forexample, the OPU gain and offset values may be different betweenwriteable and premastered portions of optical media 102. In someembodiments, optical media 102 may be zoned with a number of zones. Insome embodiments, zones of the number of zones can include both writableand premastered portions. As such, parameters can be calibrated foroperation of different media types as well as different zones. FIGS. 27Aand 27B show an embodiment of an algorithm 2700 for calibratingparameters in different regions of optical media 102.

[0399] Algorithm 2700 is called at step 2701. In step 2702, a commandstate parameter is set to calibration initialization. The top of thecalibration loop is started in step 2703. After step 2703, until thecalibration loop is completed, the algorithm is described by a statediagram. From step 2703, algorithm 2700 enters state 2704. In state2704, calibration parameters are initialized. Additionally, a currentzone parameter is set to the first zone to be calibrated.

[0400] Algorithm 2700 then transitions to state 2705. In state 2705,algorithm 2700 checks whether all zones have been calibrated. If all ofthe zones have been calibrated, then algorithm 2700 transitions fromstate 2705 to state 2713. In state 2713, the calibrated parameters arestored. In some embodiments, some or all of the parameters are stored inprogram memory 330. In some embodiments, some or all of the parameterscan be stored on optical media 102.

[0401] If algorithm 2700 determines that all of the zones are notcalibrated, then in state 2705, algorithm 2700 performs a seek operationto position actuator arm 104 at a particular zone of optical media 102.State algorithm 2705 determines a desired track position for the currentzone and, in step 2706, calls seek algorithm 557 to position OPU 103into the desired zone of optical media 102. In some embodiments, beforeseek algorithm 557 is called, algorithm 2700 may turn focus and trackingon, if focus and tracking are currently off.

[0402] If the seek algorithm initiated by algorithm 2706 fails thenalgorithm 2700 transitions from state 2705 to state 2710. In state 2710,a cleanup algorithm is executed. The cleanup algorithm may, for example,position OPU 103 at a parking position and may open focus and tracking.From state 2710, algorithm 2700 exits with an error flag set.

[0403] If, while in state 2705, algorithm 2700 detects an abort command,then algorithm 2700 transitions to state 2712. In state 2712, algorithm2700 acknowledges the abort command and transitions to state 2710 toexecute the cleanup algorithm.

[0404] If, in state 2705, the seek was successful, then algorithm 2700transitions to state 2707. In state 2707, algorithm 2700 performs thecalibrations, for example by calling a zone calibration algorithm 2711.Zone calibration algorithm 2711 executes individual calibration routinesin order to calibrate the parameters within the current zone. In state2707, if an abort condition is detected, then algorithm 2700 transitionsto state 2712. If an error condition is detected (for example, if one ofthe calibration routines returns an error condition), then algorithm2700 transitions to state 2709.

[0405] In state 2709, algorithm 2700 increments a retry counter. If theretry counter is above a certain value, then algorithm 2700 transitionsto state 2710 to exit. If the retry counter is still at acceptablelevels, then algorithm 2700 transitions to state 2705 to attempt anothertry at calibrating the current zone. In some embodiments, algorithm 2700may try to calibrate a particular zone several (e.g., about 3) timesbefore executing a failed exit in state 2710.

[0406] In state 2707, if the calibration algorithms are executed withouterror, the algorithm 2700 transitions to state 2708. In state 2708, theresults of the calibration are stored in one or more arrays 2715.Further, the current zone is incremented to point at the next zone andalgorithm 2700 transitions to state 2705 to perform calibrations in thenew current zone.

[0407]FIG. 27B shows an embodiment of zone calibration algorithm 2711which is called from state 2707 of algorithm 2700. Algorithm 2711 iscalled at step 2730. In step 2731, a command initialize flag is set. Instep 2732, drive 100 is brought to full power if drive 100 hadpreviously been asleep (or in lower power mode). In step 2733, the topof a calibration loop is started. In step 2734, and throughout algorithm2711, if an abort condition is detected then algorithm 2711 transitionsto state 2751 where the abort condition is acknowledged. Algorithm 2700then transitions to state 2750 where any cleanup routines (for example,parking OPU 103 or turning focus and tracking off) are executed. Fromstate 2750, algorithm 2700 transitions to state 2754 where error andabort flags are set. Algorithm 2700 then transitions to state 2753 wherealgorithm 2700 exits the loop started with step 2733. Finally, algorithm2711 exits at step 2756 with any abort or error flags set.

[0408] From step 2734, with no abort condition detected, algorithm 2711transitions to state 2735. In state 2735, tracking and focus are bothturned off, if they are on, in step 2736. Further, operating parameters(e.g., OPU Offsets, OPU Gains, FES Offsets, FES Gains, FES Loop Gain,Notch filter parameters, TES offsets, TES gains, TES loop gains, TES-FEScross-talk gain) for the current zone are loaded. If an error conditionis detected in state 2735, then algorithm 2711 transitions to state2737. In state 2737, if only an acceptable number of retries have beenattempted, then algorithm 2711 transitions back to state 2735 to retryinitializing operating parameters and turning tracking and focus off. Ifan unacceptable number of retries have been attempted, algorithm 2711transitions to state 2750 to eventually exit at step 2756 with errorflags set. If no errors are detected in state 2735, then algorithm 2711transitions to state 2739.

[0409] In state 2739, algorithm 2711 starts spin motor 101. As discussedin the Spin Motor disclosures, state 2739 can call algorithms to stopthe motor, start the motor, and set the spin speed in block 2738. If anabort flag is detected, algorithm 2711 can transition to state 2751. Ifan error is detected, then algorithm 2711 transitions to state 2740. Instate 2740, a retry is started. If too many retries have been attempted,then algorithm 2711 transitions to state 2750 to eventually exit at step2756 with error flags set. If not too many retries have been attempted,then algorithm 2711 transitions back to state 2739 to attempt to startspin motor 101 again.

[0410] If motor 101 is successfully started in state 2739, algorithm2711 transitions to state 2741. In state 2741, algorithm 2711 turnslaser 218 on and executes focus gain calibration 510. An embodiment offocus gain calibration 510 is shown in FIGS. 15A and 15B, which havebeen previously discussed. If an error is detected, then algorithm 2711transitions to state 2740 which, if not too many retries have beenattempted, transitions to state 2739 to retry states 2739 and 2741.Again, if too many retries are attempted, algorithm 2711 transitionsfrom state 2740 to state 2750. If an abort condition is detected instate 2741, then algorithm 2711 transitions to state 2751.

[0411] If algorithm 2711 in state 2741 successfully turns laser 218 onand executes a focus gain calibration in step 2742, then algorithm 2711transitions to state 2743. In state 2743, algorithm 2711 turns focus on.In steps 2744, state 2473 can start and stop motor 101, can set themotor speed of motor 101 to be appropriate for the current zone beingcalibrated, and can turn focus on by calling algorithm 535. Anembodiment of algorithm 535 is shown in FIG. 7A.

[0412] If an error is detected in state 2743, then algorithm 2711transitions to state 2747 to attempt a retry. If not too many retrieshave been attempted, algorithm 2711 transitions back to state 2743 toagain attempt to close focus. If too many retries have been attempted,then algorithm 2711 transitions to algorithm 2750 to shut laser 218 off,stop motor 101 and park OPU 103 before setting error flags in state 2754and exiting with error flags set in step 2756. If an abort condition isdetected, algorithm 2711 transitions to state 2751.

[0413] If state 2743 successfully closes focus, then algorithm 2711transitions to state 2745. In state 2745, calibration algorithms thatoperate with focus closed can be executed. These algorithms, in step2746, include focus loop gain calibration 522 (an embodiment of which isshown in FIG. 21), FES offset calibration 508 (embodiments of which areshown in FIGS. 16 and 17), TES Offset calibration 542 (embodiments ofwhich are shown in FIGS. 18 and 19), and TES Gain Calibration 544 (anembodiment of which is shown in FIG. 20).

[0414] If an error is detected in state 2745, then algorithm 2711transitions to state 2747 to retry the calibrations. If too many retrieshave been attempted, then algorithm 2711 transitions to state 2750 toturn tracking and focus off, turn laser 218 off, and shut motor 101 downbefore exiting at step 2756 with error flags set. If not too manyretries have been attempted, then algorithm 2711 transitions back tostate 2743 to attempt to close focus and execute the calibrationalgorithms of step 2746 again.

[0415] If state 2745 executes the calibrations of step 2746successfully, then algorithm 2711 transitions to state 2748. In state2748, algorithm 2711 closes focus and tracking. Furthermore, tracking isclosed at a particular track identified by a target PSA value. Thetarget PSA track is within the current zone. State 2748 may, in step2749, execute algorithms to start and stop motor 101, execute focusclose algorithm 535, execute close tracking algorithm 555, and executeseek algorithm 557 and one-track jump algorithm 559 in order to positionOPU 103 at the target PSA (position address).

[0416] If state 2748 detects an error, then algorithm 2711 transitionsto state 2752. In state 2752, algorithm 2711 checks to see if theallowable number of retries has been exhausted. If not, then algorithm2711 transitions back to state 2748 to attempt to close focus andtracking on the track identified by the target PSA once again. If thenumber of retries has been exhausted, the algorithm 2711 transitions tostate 2750 to shut laser 218 off, open tracking and focus, shut motor101 off, and eventually exit at step 2756 with error flags set. If anabort condition is detected, algorithm 2711 transitions to state 2751.

[0417] If state 2748 successfully closes focus and tracking at thetarget PSA, then algorithm 2711 transitions to state 2755. In state 2755calibration algorithms with both focus and tracking closed can beexecuted. These algorithms, examples of which are shown in step 2757,includes tracking loop gain calibration 562 (an embodiment of which isshown in FIG. 21), focus loop gain calibration 522 (an embodiment ofwhich is shown in FIG. 21), and TES-FES crosstalk calibration 579 (anembodiment of which is shown in FIG. 24).

[0418] If an error is detected in state 2755, then algorithm 2711transitions to state 2752 to attempt a retry as discussed above. If noerror is detected, then algorithm 2711 transitions to state 2754. Instate 2754, no error flags are set and algorithm 2711 prepares for anormal exit. In state 2753, algorithm 2711 signals that the loop startedin step 2733 is completed and algorithm 2711 exits in step 2756.

[0419] As shown in FIG. 27A, algorithm 2711 is executed through eachdefined zone on optical media 102. Therefore, a set of calibratedoperating parameters is stored with operating parameters which areappropriate for each zone of optical media 102.

[0420]FIG. 28 shows an embodiment of inverse non-linearity calibration512 in focus servo algorithm 501 and inverse non-linearity calibration547 in tracking servo algorithm 502. Non-linearity calibrations 512 and514 sets a gain versus offset (either TES offset or FES offset) tablewhich linearizes the TES or FES signals around the offset values.Non-linearity calibrations 512 and 514 can be calibrated duringalgorithm 1301 of FIG. 13. Further, non-linearity calibrations 512 and514, in some embodiments, may be executed during zone calibrationalgorithm 2700 of FIG. 27. FIG. 28 shows an embodiment of algorithm 2800which builds a table of FES gain, TES gain, TES offset, tracking loopgain and TES-FES cross-talk as a function of FES offset. In general,algorithm 2800 may provide a table of FES gain versus FES offset, TESgain versus TES offset, or other combinations of parameters that resultin linear operation of a digital servo system.

[0421] In FIG. 28, algorithm 2800 starts when called at step 2801. Instep 2802, algorithm 2800 sets a CMD_INIT flag. In step 2803, algorithm2800 turns power on so that drive 100 is fully functional (rather thanasleep). Step 2804 starts the top of a loop. If an abort condition isdetermined, then algorithm 2800 transitions to state 2822 where theabort command is acknowledged. Algorithm 2800 then transitions to state2823 which shuts drive 100 down, for example, by opening tracking andopening focus, shutting laser 218 off, and shutting motor 101 off.Algorithm 2823 then transitions to state 2820 where abort flags can beset. Algorithm 2800 then transitions to 2821 to signal that the loopstarted with step 2804 is complete before exiting at step 2825 with anabort flag set.

[0422] If no abort condition is detected in step 2805, then algorithm2800 transitions to state 2806. In state 2806, operating parameters fordrive 100 as well as the non-linearity look up table initial parametersare loaded. Further, an initial offset is set in state 2806.

[0423] If an error is detected in state 2806, for example a mailboxcommunications error, then algorithm 2800 transitions to state 2823.Algorithm 2800 shuts drive 100 off (i.e., tracking off, focus off, laser218 off, motor 101 off) and transitions to state 2820. In state 2820,error flags are set. As shown in block 2824, normal calibration valuescan be restored from memory 320 or 330 (FIG. 3). Algorithm 2800 thentransitions to state 2821 which ends the loop started in step 2804.Algorithm 2800 then exits at step 2825.

[0424] If no errors are detected in state 2806, then algorithm 2800transitions to state 2807. In state 2806, algorithm 2800 initiates a setof OPU offset values, indicated by arrays 2826. These values arespecific offsets used throughout algorithm 2800. In state 2807,algorithm 2800 sets the FES offset. Algorithm 2800 then calibrates theFES gain in algorithm 510. Further, algorithm 2800 sets a doing FES flagto TRUE and a doing TES flag to FALSE in state 2807. Algorithm 2800 thentransitions to state 2808.

[0425] In state 2808, algorithm 2800, in step 2809, insures thattracking and focus are on. If an error is detected in state 2808, thealgorithm 2800 transitions to recovery state 2818. If too manyrecoveries have been attempted in recovery state 2818, then algorithm2800 transitions to state 2823 and eventually exits with an error flagset in step 2825. If no error is detected in state 2808, then algorithmcontinues to state 2809.

[0426] If the doing FES flag is TRUE, then algorithm 2800 transitions tostate 2809. In state 2809, algorithm 2800 measures the focus loop gainat a cross-over frequency. The cross-over frequency can be, for example,1.5 kHz. Algorithm 2800 may, for example, call GetBode algorithm 2200 inFIG. 22 in step 2810. If the loop gain at the cross-over frequency isclose to unity, then algorithm 2800 sets the doing TES flag to TRUE andtransitions back to state 2808. If the loop gain is not yet unity, thenalgorithm 2800 transitions to state 2811.

[0427] In state 2811, the FES gain is adjusted. In some embodiments, theFES gain is adjusted in a first direction and if the loop gain isdetermined to be farther from unity than with the last adjusted FESgain, then the FES gain is adjusted in the opposite direction. Once theFES gain is adjusted in state 2811, then algorithm 2800 transitions tostate 2809 to re-measure the loop gain with a new FES gain. Again, if anerror is detected in state 2809, then algorithm 2800 transitions tostate 2818 to attempt a retry.

[0428] From state 2808 if doing TES is TRUE, then algorithm 2800transitions to state 2812. In state 2812, algorithm 2800 executes theTES gain calibration algorithm 544 and the TES offset calibration 542.If an error is detected in state 2812, then algorithm 2800 transitionsto state 2818 to attempt a retry. If no error is detected in state 2812,then algorithm 2800 transitions to state 2813

[0429] In state 2813, algorithm 2800 executes tracking loop gaincalibration 562 in step 2815. If an error is detected in state 2813,then algorithm 2800 transitions to state 2818. If no error is detected,then algorithm 2800 sets the doing FES flag to FALSE and the doing TESflag to FALSE and transitions to state 2816.

[0430] In state 2816, algorithm 2800 executes TES-FES crosstalk gaincalibration 579. In some embodiments, as shown in block 2817, algorithm2800 can move OPU 103 to a particular position on optical medium 102,for example the outer rim. Algorithm 2800 then transitions to state2819. In state 2819, the results of the linearity calibration for theselected FES offset is stored in arrays 2826. Algorithm 2800 may, forexample, store the results in flash memory 330. If algorithm 2800determines that algorithm 2800 is not finished (i.e., values for eachFES offset have not been determined), then algorithm 2800 transitionsback to state 2807 to pick the next FES offset value. If algorithm 2800determines that all of the FES offset values have been considered, thenalgorithm 2800 transitions to state 2820.

[0431] In state 2820, drive 100 is shut off and normal exit flags areset. Algorithm 2800 then transitions to state 2821, which ends the loopstarted with step 2804. Algorithm 2800 then exits normally at step 2825.

[0432] From algorithm 2800, a table of FES gain, TES gain, TES offset,tracking loop gain, and TES-FES crosstalk gain is tabulated for eachvalue of FES offset. These parameters are then set during operation ininverse non-linearity algorithms 511 and 546. In some embodiments, theFES and TES calculations are very sensitive to the current focusposition (the FES offset value). Algorithms 512 and 547 build a table ofgains which account for the nonlinear effects in FES and TES. Blocks 511and 546, then, can use these tables of gains to change the FES and TESgains in order to keep the response linear.

[0433]FIG. 29 shows an embodiment of a head load algorithm 2900. Whendrive 100 is started, the position of the OPU over optical media 102 isunknown. Head load algorithm 2900 allows drive 100 to be started andfocus and tracking to be closed over a valid portion (i.e., a portionwith tracks) of optical media 102. The tracking control signal (biassignal) required to position OPU 103 in an open loop mode over thetracks of optical media 102 can be quite variable due to mechanical andelectronic parameter variation and the physical orientation of drive100. Head load algorithm 2900 starts at step 2901, where optical media102 is spun up by starting spindle driver 101. In step 2902, OPU 103 isbiased against the inner stop. In other words, the tracking controleffort is set at a value that insures that OPU 103 is positioned againstthe inner stop. Algorithm 2900 then moves to step 2903. In step 2903,algorithm 2900 closes focus, for example with focus close algorithm 535.In step 2904, the bias signal is incremented to move OPU 103 slightlyaway from the inner stop. In step 2905, the TES peak to peak value iscalculated. In some embodiments, in step 2902 OPU 103 is positioned atany extreme position (e.g., at the inner diameter of optical media 102or the outer diameter of optical media 102).

[0434] In some embodiments, optical media 102 has an inner portion 153(FIG. 1B) that includes a bar code pattern over about ½ of thecircumference. The TES amplitude, while over the bar code pattern, issimilar to the TES amplitude when over premastered portion 150, but theTES waveform is different. FIGS. 30A and 30B show examples of the TESamplitude with OPU 103 over the bar code area (BCA) of optical media102. For comparison, FIG. 30C shows an example of the TES during a closetracking algorithm. In step 2905, algorithm 2900 collects TES signaldata for approximately one revolution of optical media 102. In step2906, algorithm 2900 calculates the mean of the TES signal datacollected in step 2905.

[0435] In step 2907, algorithm 2900 calculates a limit range based onthe mean calculated in step 2905 and compares each sampled data in theTES data taken in step 2905 with that limit range. Algorithm 2900 countsthe number of samples that are within the limits.

[0436] In step 2908, algorithm 2900 compares the count from step 2907 toa threshold limit. If the count is over the threshold limit, then OPU103 is over a readable portion of optical media 102 (i.e., a portionwith tracks) and algorithm 2900 proceeds to step 2909. Otherwise,algorithm 2900 returns to step 2904 to move OPU 103 out anotherincrement.

[0437] Algorithm 2900 continuous to move OPU 103 away from the innerdiameter of optical media 102 until algorithm 2900 determines that OPU103 is over a portion of optical media 102 with tracks. In step 2910,algorithm 2900 closes tracking. In some embodiments, track crossingdetector 454 can be utilized to determine if OPU 103 is moving to fast.In some embodiments, a fixed time delay after incrementing the biassignal to actuator arm 104 can be utilized.

[0438] When a newly inserted optical media 102 is inserted and drive 100is started, the tracks under OPU 103 are of an unknown type (e.g., theycould be in a writeable portion or a premastered portion of opticalmedia 102). As discussed above, there are many operating parameters thatare media dependent (e.g., TES gain and offset, FES gain and offset).The media type can be determined by starting with parameters appropriatefor a premastered portion of optical media 102 and monitoring the TESpeak-to-peak signal with focus closed. The TES peak-to-peak signal ismuch larger (for example by about twice) for writeable tracks than forpremastered tracks. In some embodiments, algorithm 2900 includes step2909 executed before tracking is closed in step 2910. In step 2903,operating parameters appropriate for writeable portions of optical disk102 are loaded. In step 2909, if the TES peak-to-peak signal is below athreshold value then algorithm 2900 loads operating parametersappropriate to a premastered portion instead.

[0439] In some embodiments, the threshold value can be set to be between50% and 100% of an expected peak-to-peak value for the TES overwriteable media. If the threshold value is set too high or too low,however, there is a greater likelihood of media miss-identification,resulting in loading of incorrect operating parameters.

[0440] CD ROM Appendix A is a computer program listing appendix thatincludes source codes for an embodiment of the present invention. Adirectory of CD ROM Appendix A is given in Appendix B. Both CD ROMAppendix A and Appendix B are herein incorporated by reference in thisapplication in their entirety.

[0441] The above detailed description describes embodiments of theinvention that are intended to be exemplary. One skilled in the art willrecognize variations that are within the scope and spirit of thisdisclosure. As such, the invention is limited only by the followingclaims.

we claim:
 1. A method of calibrating a loop gain of a loop gainamplifier in a digital servo system, comprising: receiving opticalsignals from an optical pick-up unit in an optical disk drive; closingthe digital servo system with a first loop gain, the digital servosystem calculating a control signal based on the optical signals;applying a sinusoidal disturbance at a cross-over frequency to thecontrol signal generated by the digital servo system to form a secondcontrol signal; controlling a position of the optical pick-up unit withthe second control signal; calculating a discrete Fourier transform ofthe sinusoidal disturbance at the cross-over frequency to form adisturbance DFT; calculating a discrete Fourier transform of the controlsignal to form a signal DFT; calculating a measured loop gain from aratio of the disturbance DFT and the signal DFT; and calculating theloop gain from a ratio between the first loop gain and the measured loopgain.
 2. The method of claim 1, wherein the digital servo system is atracking servo system.
 3. The method of claim 2, wherein closing thedigital servo system with a first loop gain includes closing a focusservo system with a focus loop gain; and closing the tracking servosystem with the first loop gain.
 4. The method of claim 2, wherein thecross-over frequency is about 1.8 kHz.
 5. The method of claim 1, whereinthe digital servo system is a focus servo system.
 6. The method of claim5, wherein the cross-over frequency is about 1.5 kHz.
 7. The method ofclaim 1, wherein calculating the loop gain includes dividing the firstgain by the measured loop gain and multiplying by a desired loop gain atthe second control signal.
 8. The method of claim 1, wherein the desiredloop gain is unity.
 9. An optical disk drive, comprising: an opticalpick-up unit; an analog processor coupled to receive signals fromdetectors in the optical pick-up unit and provide digital signals; atleast one processor coupled to receive the digital signals, the at leastone processor calculating at least one control signal; and a drivercoupled to control a position of the optical pick-up unit in response tothe at least one control signal, wherein the at least one processorexecutes an algorithm that closes a digital servo system with a loopgain amplifier with a first loop gain, the digital servo systemcalculating a control signal based on the digital signals, applies asinusoidal disturbance at a cross-over frequency to the control signalgenerated by the digital servo system to form a second control signal,substitutes the second control signal for the control signal, calculatesa discrete Fourier transform of the sinusoidal disturbance at thecross-over frequency to form a disturbance DFT, calculates a discreteFourier transform of the control signal to form a signal DFT, calculatesa measured loop gain from a ratio of the disturbance DFT and the signalDFT, and calculates a loop gain from a ratio between the first loop gainand the measured loop gain.
 10. The drive of claim 9, wherein thedigital servo system is a tracking servo system.
 11. The drive of claim10, wherein closing the digital servo system with a first loop gainincludes closing a focus servo system with a focus loop gain; andclosing the tracking servo system with the first loop gain.
 12. Thedrive of claim 10, wherein the cross-over frequency is about 1.8 kHz.13. The drive of claim 9, wherein the digital servo system is a focusservo system.
 14. The drive of claim 13, wherein the cross-overfrequency is about 1.5 kHz.
 15. The drive of claim 9, wherein the loopgain is calculated by dividing the first gain by the measured loop gainand multiplying by a desired loop gain at the second control signal. 16.The drive of claim 15, wherein the desired loop gain is unity.
 17. Anoptical disk drive, comprising: means for controlling a position of anoptical pick-up unit based on optical signals; and means for calibratinga loop gain of the means for controlling.